Precoding matrix codebook design and periodic channel state information feedback for advanced wireless communication systems

ABSTRACT

Channel quality indicator (CQI) and precoding feedback from a user equipment includes reporting of at least a first and a second precoding matrix indicator (PMI). First, second and third indices are determined based upon the first and the second PMI and third and fourth PMI and are employed to select the precoding matrix. The selected precoding matrix includes a first column comprising a first row partition and a second row partition, where the first row partition is a Kronecker product of at least first and second precoding vectors and the second row partition is a Kronecker product of a first term and a second term. The first term is a product of a co-phasing factor and the first precoding vector and the second term is the second precoding vector. The first precoding vector is selected from a first codebook and the second precoding vector is selected from a second codebook.

This application claims priority to and hereby incorporates by reference U.S. Provisional Patent Application No. 61/973,088, filed Mar. 31, 2014, entitled “SYSTEMS AND METHODS FOR PUCCH FEEDBACK FOR ADVANCED WIRELESS COMMUNICATION SYSTEMS” and U.S. Provisional Patent Application No. 61/986,614, filed Apr. 30, 2014, entitled “PRECODING MATRIX CODEBOOK DESIGN AND PERIODIC CHANNEL STATE INFORMATION FEEDBACK FOR ADVANCED WIRELESS COMMUNICATION SYSTEMS.”

TECHNICAL FIELD

The present disclosure relates generally to wireless communication systems with multiple antenna elements, and more specifically to periodic channel status information (CSI) feedback for use in a system with multiple active antenna elements arranged in a two-dimensional panel.

BACKGROUND

In frequency division, multiple input multiple output systems wireless communications systems, the user equipment needs to feedback not only a precoding matrix indicator for the azimuth domain (also called the horizontal domain) but also a precoding matrix indicator for the elevation domain (also called the vertical domain). On the other hand, to maintain good feedback reliability and coverage, physical uplink control channel quality information feedback designs are subject to payload size constraints.

There is, therefore, a need in the art for improved channel quality information feedback for frequency division, multiple input multiple output systems wireless communications systems.

SUMMARY

Channel quality indicator (CQI) and precoding feedback from a user equipment includes reporting of at least a first and a second precoding matrix indicator (PMI). First, second and third indices are determined based upon the first and the second PMI and third and fourth PMI and are employed to select the precoding matrix. The selected precoding matrix includes a first column comprising a first row partition and a second row partition, where the first row partition is a Kronecker product of at least first and second precoding vectors and the second row partition is a Kronecker product of a first term and a second term. The first term is a product of a co-phasing factor and the first precoding vector and the second term is the second precoding vector. The first precoding vector is selected from a first codebook and the second precoding vector is selected from a second codebook.

Before undertaking the DETAILED DESCRIPTION below, it may be advantageous to set forth definitions of certain words and phrases used throughout this patent document: the terms “include” and “comprise,” as well as derivatives thereof, mean inclusion without limitation; the term “or,” is inclusive, meaning and/or; the phrases “associated with” and “associated therewith,” as well as derivatives thereof, may mean to include, be included within, interconnect with, contain, be contained within, connect to or with, couple to or with, be communicable with, cooperate with, interleave, juxtapose, be proximate to, be bound to or with, have, have a property of, or the like; and the term “controller” means any device, system or part thereof that controls at least one operation, where such a device, system or part may be implemented in hardware that is programmable by firmware or software. It should be noted that the functionality associated with any particular controller may be centralized or distributed, whether locally or remotely. Definitions for certain words and phrases are provided throughout this patent document, those of ordinary skill in the art should understand that in many, if not most instances, such definitions apply to prior, as well as future uses of such defined words and phrases.

BRIEF DESCRIPTION OF THE DRAWINGS

For a more complete understanding of the present disclosure and its advantages, reference is now made to the following description taken in conjunction with the accompanying drawings, in which like reference numerals represent like parts:

FIG. 1 illustrates a wireless communication system that may employ a precoding matrix design and periodic channel state information feedback according to some embodiments of the present disclosure;

FIG. 1A illustrates a two-row, four-column, cross-polarized, two-dimensional logical antenna array that may be employed within the wireless communication system of FIG. 1;

FIG. 1B illustrates a four-row, four-column, cross-polarized, two-dimensional logical antenna array that may be employed within the wireless communication system of FIG. 1;

FIG. 1C illustrates logical port to antenna port mapping that may be employed within the wireless communication system of FIG. 1 according to some embodiments of the current disclosure;

FIG. 2 illustrates a design for PUCCH mode 1-1 submode 1 in accordance with one embodiment of the present disclosure;

FIG. 3 illustrates a second design of PUCCH mode 1-1 submode 1 in accordance with one embodiment of the present disclosure;

FIG. 4 illustrates a third design of PUCCH mode 1-1 submode 1 in accordance with one embodiment of the present disclosure;

FIG. 5 illustrates a design for PUCCH mode 1-1 submode 2 in accordance with one embodiment of the present disclosure;

FIG. 6 illustrates a second design of PUCCH mode 1-1 submode 2 in accordance with one embodiment of the present disclosure;

FIG. 7 illustrates a design for PUCCH mode 2-1 with PTI=0 in accordance with one embodiment of the present disclosure;

FIGS. 8A and 8B illustrate two alternative designs of PUCCH mode 2-1 with PTI=1 in accordance with one embodiment of the present disclosure;

FIG. 9 illustrates another design for PUCCH mode 2-1 with PTI=0 in accordance with one embodiment of the present disclosure;

FIG. 10 illustrates another design for PUCCH mode 2-1 with PTI=1 in accordance with one embodiment of the present disclosure;

FIG. 11 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure;

FIG. 12 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure;

FIG. 13 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure;

FIG. 14 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure;

FIG. 15 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure;

FIGS. 16A and 16B illustrate vertical orientations between a base station and user equipment according to some embodiments of the present disclosure;

FIG. 17 illustrates rank 1 vertical precoding matrix information distribution according to some embodiments of the present disclosure; and

FIG. 18 illustrates one to one mapping between antenna port and cross-polarized antenna elements according to some embodiments of the present disclosure.

DETAILED DESCRIPTION

FIGS. 1 through 15, discussed below, and the various embodiments used to describe the principles of the present disclosure in this patent document are by way of illustration only and should not be construed in any way to limit the scope of the disclosure. Those skilled in the art will understand that the principles of the present disclosure may be implemented in any suitably arranged wireless communication system.

The following documents are incorporated herein by reference:

-   -   [REF1] 3GPP TS 36.211: “Evolved Universal Terrestrial Radio         Access (E-UTRA); Physical channels and modulation.”     -   [REF2] 3GPP TS 36.212, “E-UTRA, Multiplexing and Channel         coding.”     -   [REF3] 3GPP TS 36.213, “E-UTRA, Physical Layer Procedures.”

List of Acronyms

AP: antenna port(s)

CB: codebook

CW: codeword

MIMO: multiple-input-multiple-output

SU-MIMO: single-user MIMO

MU-MIMO: multi-user MIMO

3GPP: 3rd Generation Partnership Project

LTE: Tong-Term Evolution

UE: user equipment

eNB: eNodeB or evolved Node B

(P)RB: (physical) resource block

DMRS: demodulation reference signal(s)

UE-RS: UE-specific reference signal(s)

CSI-RS: channel state information reference signals

MCS: modulation and coding scheme

RE: resource element

CQI: channel quality information

PMI: precoding matrix indicator

PTI: precoding type indicator

RI: rank indicator

MU-CQI: multi-user CQI

CSI: channel state information

CSI-IM: CSI interference measurement

CoMP: coordinated multi-point

NZP: non-zero power

DCI: downlink control information

DFT: Discrete Fourier Transform

DL: downlink

UL: uplink

PDSCH: physical downlink shared channel

PDCCH: physical downlink control channel

PUSCH: physical uplink shared channel

PUCCH: physical uplink control channel

The present disclosure generally relates to wireless communication systems with multiple antenna elements, and more specifically relates to periodic channel status information (CSI) feedback for use in a system with multiple active antenna elements arranged in a two-dimensional panel. FIG. 1 illustrates operation of a wireless communication system according to some embodiments of the present disclosure. The UEs depicted in FIG. 1 each include: an antenna array; a receiver or transceiver coupled to the antenna array for demodulating received wireless signals, including reference signals such as CSI-RS; a controller or processor coupled to the receiver for estimating one or more channels between the respective UE and a base station, deriving channel quality information for the channels using the reference signals and one or more of the processes described below, and reporting at least the CQI and one or more indicators of precoding matrix selection(s) to the base station as described in further detail below; and a transmitter or the transceiver coupled to the processor/controller for transmitting feedback including the CQI and/or PMI report to the base station as discussed in further detail below. Each base station likewise includes at least an antenna array for transmitting and receiving signals, a receiver chain, a controller, and a transmitter chain. In the example depicted, user equipment (UE) UE0 receives streams from evolved Node B (eNB) 100. eNB 100 multiplexes data streams intended for UE1 and UE3 and data streams intended for UE2 and UE4. The communication system thus consists of a downlink (DL), where signals are transmitted from eNB, base station (BS), NodeBs or transmission point (TP) to user equipment, and an uplink (UL), where signals are transmitted from UE to BS or NodeB. A UE, also commonly referred to as a terminal or a mobile station, may be fixed or mobile and may be a cellular phone, a personal computer device, etc. An eNB, which is generally a fixed station, may also be referred to as an access point or other equivalent terminology. DL signals include data signals conveying information content, control signals conveying DL Control Information (DCI), and Reference Signals (RS), which are also known as pilot signals. The eNB transmits data information or DCI through respective Physical DL Shared CHannels (PDSCHs) or Physical DL Control CHannels (PDCCHs). The eNB transmits one or more of multiple types of RS including a UE-Common RS (CRS), a Channel State Information RS (CSI-RS), and a DeModulation RS (DMRS). A CRS is transmitted over a DL system Bandwidth (BW) and can be used by UEs to demodulate data or control signals or to perform measurements. For CSI estimation corresponding to a number of transmit antenna ports, the eNodeB may transmit CSI-RS in addition to the CRS.

The present disclosure deals with PUCCH periodic CSI feedback designs for FD-MIMO systems equipped with a two dimensional antenna array. In the LTE Release 8 and Release 10 standards; PUCCH periodic CSI feedback is designed to provide BS or eNB with coarse channel status information observed at UE, as PUCCH has narrow data pipe and limited capacity. Therefore, unlike PUSCH designs, PUCCH CSI feedback designs places feedback reliability and coverage as the first priority, over downlink throughput optimization. In the 3GPP Release 10, there are three types of PUCCH reporting modes that are extended from Release 8 to support the double codebook structure: (1) PUCCH Mode 1-1 Submode 1; (2) PUCCH Mode 1-1 Submode 2; and (3) PUCCH Mode 2-1. The present disclosure considers a Kronecker product type codebook structure, in which the overall codebook is the Kronecker product of a horizontal codebook (H-codebook) and a vertical codebook (V-codebook). Hence, in FD-MIMO systems using a Kronecker product codebook, UE needs to feedback not only PMI for the azimuth domain (also called the horizontal domain), but also PMI for the elevation domain (also called the vertical domain). In other words, PUCCH CSI feedback for FD-MIMO UEs has to carry more PMI than that adopted in Release 8 and Release 10 standards. On the other hand, to maintain good feedback reliability and coverage, PUCCH CSI feedback designs are subject to payload size constraints. The present disclosure describes a design for PUCCH CSI feedback that accommodates increased PMI feedback while maintaining feedback reliability and coverage. In particular, the proposed PUCCH designs in this disclosure keep the same payload size as counterparts specified in Release 10 PUCCH. In this disclosure, two particular antenna configurations are considered: 2 vertical APs with 8 horizontal APs; and 4 vertical APs with 8 horizontal APs.

Release 8 2-Tx and 4-Tx Codebook (CB)

For transmission on two antenna ports, p ∈ {0,1}, and for the purpose of CSI reporting based on two antenna ports p ∈ {0,1} or p ∈ {15,16}, the precoding matrix W(i) shall be selected from TABLE 1 below, or a subset thereof:

TABLE 1 Codebook for transmission on APs {0,1} and for CSI reporting based on APs {0,1} or {15,16} Number of layers υ Codebook Index 1 2 0 $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ 1 \end{bmatrix}$ $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & 0 \\ 0 & 1 \end{bmatrix}$ 1 $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ {- 1} \end{bmatrix}$ $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & 1 \\ 1 & {- 1} \end{bmatrix}$ 2 $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ j \end{bmatrix}$ $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & 1 \\ j & {- j} \end{bmatrix}$ 3 $\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ {- j} \end{bmatrix}$ — For the closed-loop spatial multiplexing transmission mode defined in 3GPP TS 36.213 [REF3], the codebook index 0 is not used when the number of layers is υ=2.

For transmission on four antenna ports, p ∈ {0,1,2,3}, the precoding matrix W shall be selected from TABLE 2 or a subset thereof. For the purpose of CSI reporting based on four antenna ports p ∈ {0,1,2,3} or p ∈ {15,16,17,18}, the precoding matrix W shall be selected from TABLE 2 or a subset thereof except for alternativeCodeBookEnabledFor4TX−r12=TRUE, in which case the precoding matrix W shall be selected from Tables 7.2.4-0A, 7.2.4-0B, 7.2.4-0C, 7.2.4-0D in [REF3] or a subset thereof. The quantity W_(n) ^({s}) denotes the matrix defined by the columns given by the set {s} from the expression

W_(n) = I − 2u_(n)u_(n)^(H)/u_(n)^(H)u_(n),

where I is the 4×4 identity matrix and the vector u_(n) is given by TABLE 2:

TABLE 2 Codebook for transmission on APs {0,1,2,3} and for CSI reporting based on APs {0,1,2,3} or {15,16,17,18} Code- book Number of layers υ Index u_(n) 1 2 3 4 0 u₀ = [1 −1 −1 −1]^(T) W₀ ^({1}) W₀ ^({14})/√2 W₀ ^({124})/√3 W₀ ^({1234})/2 1 u₁ = [1 −j 1 j]^(T) W₁ ^({1}) W₁ ^({12})/√2 W₁ ^({123})/√3 W₁ ^({1234})/2 2 u₂ = [1 1 −1 1]^(T) W₂ ^({1}) W₂ ^({12})/√2 W₂ ^({123})/√3 W₂ ^({3214})/2 3 u₃ = [1 j 1 −j]^(T) W₃ ^({1}) W₃ ^({12})/√2 W₃ ^({123})/√3 W₃ ^({3214})/2 4 $u_{4} = \begin{bmatrix} 1 & {\left( {{- 1} - j} \right)/\sqrt{2}} & {- j} & {\left( {1 - j} \right)/\sqrt{2}} \end{bmatrix}^{T}$ W₄ ^({1}) W₄ ^({14})/√2 W₄ ^({124})/√3 W₄ ^({1234})/2 5 $u_{5} = \begin{bmatrix} 1 & {\left( {1 - j} \right)/\sqrt{2}} & j & {\left( {{- 1} - j} \right)/\sqrt{2}} \end{bmatrix}^{T}$ W₅ ^({1}) W₅ ^({14})/√2 W₅ ^({124})/√3 W₅ ^({1234})/2 6 $u_{6} = \begin{bmatrix} 1 & {\left( {1 + j} \right)/\sqrt{2}} & {- j} & {\left( {{- 1} + j} \right)/\sqrt{2}} \end{bmatrix}^{T}$ W₆ ^({1}) W₆ ^({13})/√2 W₆ ^({134})/√3 W₆ ^({1324})/2 7 $u_{7} = \begin{bmatrix} 1 & {\left( {{- 1} + j} \right)/\sqrt{2}} & j & {\left( {1 + j} \right)/\sqrt{2}} \end{bmatrix}^{T}$ W₇ ^({1}) W₇ ^({13})/√2 W₇ ^({134})/√3 W₇ ^({1324})/2 8 u₈ = [1 −1 1 1]^(T) W₈ ^({1}) W₈ ^({12})/√2 W₈ ^({124})/√3 W₈ ^({1234})/2 9 u₉ = [1 −j −1 −j]^(T) W₉ ^({1}) W₉ ^({14})/√2 W₉ ^({134})/√3 W₉ ^({1234})/2 10 u₁₀ = [1 1 1 −1]^(T) W₁₀ ^({1}) W₁₀ ^({13})/√2 W₁₀ ^({123})/√3 W₁₀ ^({1324})/2 11 u₁₁ = [1 j −1 j]^(T) W₁₁ ^({1}) W₁₁ ^({13})/√2 W₁₁ ^({134})/√3 W₁₁ ^({1324})/2 12 u₁₂ = [1 −1 −1 1]^(T) W₁₂ ^({1}) W₁₂ ^({12})/√2 W₁₂ ^({123})/√3 W₁₂ ^({1234})/2 13 u₁₃ = [1 −1 1 −1]^(T) W₁₃ ^({1}) W₁₃ ^({13})/√2 W₁₃ ^({123})/√3 W₁₃ ^({1324})/2 14 u₁₄ = [1 1 −1 −1]^(T) W₁₄ ^({1}) W₁₄ ^({13})/√2 W₁₄ ^({123})/√3 W₁₄ ^({3214})/2 15 u₁₅ = [1 1 1 1]^(T) W₁₅ ^({1}) W₁₅ ^({12})/√2 W₁₅ ^({123})/√3 W₁₅ ^({1234})/2

Release 12 4-Tx Enhanced CB and 8-Tx CB

In Release-10 8-Tx CB and Release-12 4-Tx enhanced CB, the double codebook structure is adopted. In the double codebook structure, the codebook W can be written as the product of the inner codebook W₁ and the outer codebook W₂, i.e., W=W₁W₂, where W₁ is used to capture the long-term wideband channel characteristics and W₂ is used to capture the short-teen frequency-selective channel characteristics. A inner codeword (CW), W₁(i), has a block diagonal structure depicted as the follows:

${W_{1}(i)} = \begin{bmatrix} {X(i)} & 0 \\ {X(i)} & {X(i)} \end{bmatrix}$

where X(i) is a matrix defined as follows:

X(i)=└b _(2imod32) b _((2i+1)mod32) b _((2i+2)mod32) b _((2i+3)mod32)┘

with b_(n)=[1 e^(j2πn/32) e^(j2π2n/32) e^(j2π3n/32)]^(T). The outer codebook W₂ performs two functions: beam selection and co-phasing. For rank 1, the outer codebook W₂ is chosen to be

$W_{2} = \begin{Bmatrix} \begin{bmatrix} Y_{1} \\ Y_{1} \end{bmatrix} & \begin{bmatrix} Y_{1} \\ {- Y_{1}} \end{bmatrix} & \begin{bmatrix} Y_{1} \\ {j\; Y_{1}} \end{bmatrix} & \begin{bmatrix} Y_{1} \\ {{- j}\; Y_{1}} \end{bmatrix} \end{Bmatrix}$

where Y₁ ∈ {e₁, e₂, . . . e₄} with e_(i) being the i-th column vector of a 4×4 identity matrix. The index i of the vector e_(i) is called the beam selection index. There are total 16 codewords (4 bit codebook). For rank 2, the outer codebook W₂ is chosen to be

$W_{2} = \begin{Bmatrix} \begin{bmatrix} Y_{1} & Y_{2} \\ Y_{1} & {- Y_{2}} \end{bmatrix} & \begin{bmatrix} Y_{1} & Y_{2} \\ {j\; Y_{1}} & {{- j}\; Y_{2}} \end{bmatrix} \end{Bmatrix}$

where (Y₁, Y₂)∈ {(e₁, e₁), (e₂, e₂), (e₃, e₃), (e₄, e₄), (e₁, e₂), (e₁, e₃), (e₂, e₃), (e₁, e₄)}. There are total 16 codewords (4 bit codebook).

For 8 antenna ports, each PMI value corresponds to a pair of codebook indices given in Table 7.2.4-1, 7.2.4-2, 7.2.4-3, 7.2.4-4, 7.2.4-5, 7.2.4-6, 7.2.4-7, or 7.2.4-8 in 3GPP TS36.213, where the quantities φ_(m) and ν_(m), are given by

φ_(m) =e ^(jπn/2)

ν_(m)=[1 e ^(j2πn/32) e ^(j4πn/32) e ^(j6πn/32)]^(T).

-   -   For 8 antenna ports {15,16,17,18,19,20,21,22}, a first PMI value         of i₁ ∈ {0,1, . . . f(υ)−1} and a second PMI value of i₂ ∈ {0,1,         . . . gυ)−1} correspond to the codebook indices i₁ and i₂ given         in Table 7.2.4-j in 3GPP TS36.213, with v equal to the         associated RI value and where j=υ, f (υ)={16,16,4,4,4,4,4,1} and         g(υ)={16,16,16,8,1,1,1,1}. For υ=1 and 2, corresponding tables         are provided in TABLE 3 and TABLE 4 below.     -   In some cases codebook subsampling is supported. The sub-sampled         codebook for PUCCH mode 1-1 submode 2 is defined in Table         7.2.2-1D for first and second precoding matrix indicator i₁ and         i₂. Joint encoding of rank and the first precoding matrix         indicator i₁ for PUCCH mode 1-1 submode 1 is defined in Table         7.2.2-1E in 3GPP TS36.213. The sub-sampled codebook for PUCCH         mode 2-1 is defined in Table 7.2.2-1F in 3GPP TS36.213 for PUCCH         Reporting Type 1a.

TABLE 3 Codebook for 1-layer CSI reporting using antenna ports 15 to 22 i₂ i₁ 0 1 2 3 4 5 6 7 0-15 W_(2i) ₁ _(,0) ⁽¹⁾ W_(2i) ₁ _(,1) ⁽¹⁾ W_(2i) ₁ _(,2) ⁽¹⁾ W_(2i) ₁ _(,3) ⁽¹⁾ W_(2i) ₁ _(+1,0) ⁽¹⁾ W_(2i) ₁ _(+1,1) ⁽¹⁾ W_(2i) ₁ _(+1,2) ⁽¹⁾ W_(2i) ₁ _(+1,3) ⁽¹⁾ i₂ i₁ 8 9 10 11 12 13 14 15 0-15 W_(2i) ₁ _(+2,0) ⁽¹⁾ W_(2i) ₁ _(+2,1) ⁽¹⁾ W_(2i) ₁ _(+2,2) ⁽¹⁾ W_(2i) ₁ _(+2,3) ⁽¹⁾ W_(2i) ₁ _(+3,0) ⁽¹⁾ W_(2i) ₁ _(+3,1) ⁽¹⁾ W_(2i) ₁ _(+3,2) ⁽¹⁾ W_(2i) ₁ _(+3,3) ⁽¹⁾ ${{where}\mspace{14mu} W_{m,n}^{(1)}} = {\frac{1}{\sqrt{8}}\begin{bmatrix} v_{m} \\ {\phi_{n}v_{m}} \end{bmatrix}}$

TABLE 4 Codebook for 2-layer CSI reporting using antenna ports 15 to 22 i₂ i₁ 0 1 2 3 0-15 W_(2i) ₁ _(,2i) ₁ _(,0) ⁽²⁾ W_(2i) ₁ _(,2i) ₁ _(,1) ⁽²⁾ W_(2i) ₁ _(+1,2i) ₁ _(+1,0) ⁽²⁾ W_(2i) ₁ _(+1,2i) ₁ _(+1,1) ⁽²⁾ i₂ i₁ 4 5 6 7 0-15 W_(2i) ₁ _(+2,2i) ₁ _(+2,0) ⁽²⁾ W_(2i) ₁ _(+2,2i) ₁ _(+2,1) ⁽²⁾ W_(2i) ₁ _(+3,2i) ₁ _(+3,0) ⁽²⁾ W_(2i) ₁ _(+3,2i) ₁ _(+3,1) ⁽²⁾ i₂ i₁ 8 9 10 11 0-15 W_(2i) ₁ _(,2i) ₁ _(+1,0) ⁽²⁾ W_(2i) ₁ _(,2i) ₁ _(+1,1) ⁽²⁾ W_(2i) ₁ _(+1,2i) ₁ _(+2,0) ⁽²⁾ W_(2i) ₁ _(+1,2i) ₁ _(+2,1) ⁽²⁾ i₂ i₁ 12 13 14 15 0-15 W_(2i) ₁ _(,2i) ₁ _(+3,0) ⁽²⁾ W_(2i) ₁ _(,2i) ₁ _(+3,1) ⁽²⁾ W_(2i) ₁ _(+1,2i) ₁ _(+3,0) ⁽²⁾ W_(2i) ₁ _(+1,2i) ₁ _(+3,1) ⁽²⁾ ${{where}\mspace{14mu} W_{m,m^{\prime},n}^{(2)}} = {\frac{1}{4}\begin{bmatrix} v_{m} & v_{m^{\prime}} \\ {\phi_{n}v_{m}} & {{- \phi_{n}}v_{m^{\prime}}} \end{bmatrix}}$

CSI Feedback

In the LTE/LTE-Advanced cellular communication systems, UE needs to report rank indicator (RI), precoding matrix indicator (PMI), and channel quality indicator (CQI) in order to support link adaption and precoders used at eNB. There are two types of CSI feedback, periodic feedback and aperiodic feedback, described as follows:

Aperiodic Feedback on PUSCH:

PUSCH has relatively large data pipe and thus has relatively loose constraints on the feedback payload size. The CSI report via PUSCH is self-contained in the sense that CQI, PMI, and RI are reported together in one slot of the same subframe. For different PUSCH reporting modes, the frequency granularities of CQI and PMI are different (subband versus wideband) while RI always remains for wideband.

Periodic Feedback on PUCCH:

A UE is semi-statically configured by higher layers to periodically feedback CQI, PMI, PTI, and/or RI on the PUCCH using the reporting modes given TABLE 5. The details for each PUCCH CSI reporting modes can be found in [REF3]. Compared with PUSCH, PUCCH has limited capacity and narrow data pipe. For each rank, the maximum payload size is 11 bits. To meet feedback payload size constraints, codebook subsampling may be required. Unlike that for PUCCH, the CSI report for PUSCH consists of RI, PMI, and CQI that are transmitted in more than one subframe.

TABLE 5 Codebook for 2-layer CSI reporting using antenna ports 15 to 22 PMI Feedback Type No PMI Single PMI PUCCH CQI Wideband Mode 1-0 Mode 1-1 Feedback Type (wideband CQI) UE Selected Mode 2-0 Mode 2-1 (subband CQI)

Feedback Timing:

For a UE configured in transmission mode 1-9 and for each serving cell, or for a UE configured in transmission mode 10 and for each CSI process in each serving cell, the periodicity N_(pd) (in subframes) and offset N_(OFFSET,CQI) (in subframes) for CQI/PMI reporting are determined based on the parameter cqi-pmi-ConfigIndex(I_(CQI/PMI)) given in Table 7.2.2-1A in 3GPP TS36.213 for FDD. The periodicity M_(RI) and relative offset N_(OFFSET,RI) for RI reporting are determined based on the parameter ri-ConfigIndex(I_(RI)) given in Table 7.2.2-1C in 3GPP TS36.213. Both cqi-pmi-ConfigIndex and ri-ConfigIndex are configured by higher layer signaling. The relative reporting offset for RI N_(OFFSET,RI) takes values from the set {0,−1, . . . −(N_(pd)−1)}. If a UE is configured to report for more than one CSI subframe set then parameters cqi-pmi-ConfigIndex and ri-ConfigIndex respectively correspond to the CQI/PMI and RI periodicity and relative reporting offset for subframe set 1 and parameters cqi-pmi-ConfigIndex2 and ri-ConfigIndex2 respectively correspond to the CQI/PMI and RI periodicity and relative reporting offset for subframe set 2. For a UE configured with transmission mode 10, the parameters cqi-pmi-ConfigIndex, ri-ConfigIndex, cqi-pmi-ConfigIndex2 and ri-ConfigIndex2 can be configured for each CSI process.

In the case where wideband CQI/PMI reporting is configured:

-   -   The reporting instances for wideband CQI/PMI are subframes         satisfying (10×n_(f)+└n_(s)/2┘−N_(OFFSET,CQI))mod(N_(pd))=0,         where n_(f) is the system frame number and n_(s) is the slot         index within the frame.     -   In case RI reporting is configured, the reporting interval of         the RI reporting is an integer multiple M_(RI) of period N_(pd)         (in subframes).         -   The reporting instances for RI are subframes satisfying             (10×n_(f)+└n_(s)/2┘−N_(OFFSET,CQI)−N_(OFFSET,RI))mod(N_(pd)·M_(RI))=0.

In the case where both wideband CQI/PMI and subband CQI reporting are configured:

-   -   4The reporting instances for wideband CQI/PMI and subband CQI         are subframes satisfying         (10×n_(f)+└n_(s)/2┘−N_(OFFSET,CQI))mod(N_(pd))=0.         -   When PTI is not transmitted (due to not being configured) or             the most recently transmitted PTI is equal to 1 for a UE             configured in transmission modes 8 and 9, or for a UE             configured in transmission mode 10 without a “RI-reference             CSI process” for a CSI process, or the transmitted PTI is             equal to 1 reported in the most recent RI reporting instance             for a CSI process when a UE is configured in transmission             mode 10 with a “RI-reference CSI process” for the CSI             process, or the transmitted PTI is equal to 1 for a             “RI-reference CSI process” reported in the most recent RI             reporting instance for a CSI process when a UE is configured             in transmission mode 10 with the “RI-reference CSI process”             for the CSI process, and the most recent type 6 report for             the CSI process is dropped:             -   The wideband CQI/wideband PMI (or wideband CQI/wideband                 second PMI for transmission modes 8, 9 and 10) report                 has period H·N_(pd), and is reported on the subframes                 satisfying                 (10×n_(f)+└n_(s)/2┘−N_(OFFSET,CQI))mod((H·N_(pd))=0. The                 integer H is defined as H=J·K+1, where J is the number                 of bandwidth parts.             -   Between every two consecutive wideband CQI/wideband PMI                 (or wideband CQI/wideband second PMI for transmission                 modes 8, 9 and 10) reports, the remaining J·K reporting                 instances are used in sequence for subband CQI reports                 on K full cycles of bandwidth parts except when the gap                 between two consecutive wideband CQI/PMI reports                 contains less than J·K reporting instances due to a                 system frame number transition to 0, in which case the                 UE shall not transmit the remainder of the subband CQI                 reports which have not been transmitted before the                 second of the two wideband CQI/wideband PMI (or wideband                 CQI/wideband second PMI for transmission modes 8, 9                 and 10) reports. Each full cycle of bandwidth parts                 shall be in increasing order starting from bandwidth                 part 0 to bandwidth part J−1. The parameter K is                 configured by higher-layer signaling.     -   When the most recently transmitted PTI is 0 for a UE configured         in transmission modes 8 and 9 or for a UE configured in         transmission mode 10 without a “RI-reference CSI process” for a         CSI process, or the transmitted PTI is 0 reported in the most         recent RI reporting instance for a CSI process when a UE is         configured in transmission mode 10 with a “RI-reference CSI         process” for the CSI process, or the transmitted PTI is 0 for a         “RI-reference CSI process” reported in the most recent RI         reporting instance for a CSI process when a UE is configured in         transmission mode 10 with the “RI-reference CSI process” for the         CSI process, and the most recent type 6 report for the CSI         process is dropped:         -   The wideband first precoding matrix indicator report has             period H′·N_(pd), and is reported on the subframes             satisfying             (10×n_(f)+└n_(s)/2┘−N_(OFFSET,CQI))mod(H′·N_(pd))=0, where             H′ is signaled by higher layers.         -   Between every two consecutive wideband first precoding             matrix indicator reports, the remaining reporting instances             are used for a wideband second precoding matrix indicator             with wideband CQI.     -   In case RI reporting is configured, the reporting interval of RI         is M_(RI) times the wideband CQI/PMI period H·N_(pd), and RI is         reported on the same PUCCH cyclic shift resource as both the         wideband CQI/PMI and subband CQI reports. The reporting         instances for RI are subframes satisfying:         (10×n_(f)+└n_(s)/2├−N_(OFFSET,CQI)−N_(OFFSET,RI))mod(H·N_(pd)·M_(RI))=0

The sub-sampled codebook for PUCCH mode 1-1 submode 2 for 8 CSI-RS ports is defined in TABLE 6 for first and second precoding matrix indicator i₁ and i₂:

TABLE 6 PUCCH mode 1-1 submode 2 codebook subsampling Relationship between Relationship between the first PMI value the second PMI value and codebook index i₁ and codebook index i₂ Value of Value of the first Codebook the second Codebook Total RI PMI I_(PMI1) index i₁ PMI I_(PMI2) index i₂ # bits 1 0-7 2I_(PMI1) 0-1 2I_(PMI2) 4 2 0-7 2I_(PMI1) 0-1  I_(PMI2) 4 3 0-1 2I_(PMI1) 0-7 4 · [I_(PMI2)/4] + I_(PMI2) 4 4 0-1 2I_(PMI1) 0-7 I_(PMI2) 4 5 0-3  I_(PMI1) 0 0 2 6 0-3  I_(PMI1) 0 0 2 7 0-3  I_(PMI1) 0 0 2 8 0 0 0 0 0 TABLE 7 shows PUCCH mode 2-1 codebook subsampling for the second PMI feedback:

TABLE 7 PUCCH mode 1-1 submode 2 codebook subsampling Relationship between the second PMI value and codebook index i₂ Value of the second Codebook RI PMI I_(PMI2) index i₂ 1  0-15  I_(PMI2) 2 0-3 2I_(PMI2) 3 0-3 8 · [I_(PMI2)/2] + (I_(PMI2) mod2) + 2 4 0-3 2I_(PMI2) 5 0 0 6 0 0 7 0 0 8 0 0

The present disclosure deals with PUCCH periodic CSI feedback designs for FD-MIMO systems equipped with a two dimensional antenna array. In the LTE Release 8 and Release 10 standards, PUCCH periodic CSI feedback is designed to provide BS or NodeB with coarse channel status information observed at UE, as PUCCH has narrow data pipe and limited capacity. Therefore, unlike PUSCH designs, PUCCH CSI feedback designs place feedback reliability and coverage as the first priority instead of downlink throughput optimization. In the 3GPP Release 10, there are three types of PUCCH reporting modes that are extended from Release 8 to support the double codebook structure. These three PUCCH reporting modes in Release 10 are listed as follows: 1) PUCCH Mode 1-1 Submode 1, 2) PUCCH Mode 1-1 Submode 2, and 3) PUCCH Mode 2-1. This disclosure considers a Kronecker product type codebook structure, in which the overall codebook is the Kronecker product of a horizontal codebook (H-codebook) and a vertical codebook (V-codebook). Hence, in FD-MIMO systems using a Kronecker product codebook, UE needs to feedback not only PMI for the azimuth domain (also called the horizontal domain), but also PMI for the elevation domain (also called the vertical domain). In other words, PUCCH CSI feedback for FD-MIMO UEs has to carry more PMI than the ones adopted in Release 8 and Release 10 standards. On the other hand, to maintain good feedback reliability and coverage, PUCCH CSI feedback designs are subject to payload size constraints. This disclosure describes a design for PUCCH CSI feedback to accommodate increased PMI feedback while maintaining feedback reliability and coverage. In particular, the proposed PUCCH designs in this disclosure keep the same payload size as one specified in Release 10 PUCCH. In this disclosure, two particular antenna configurations, two vertical antenna patches (APs) with eight horizontal APs, and four vertical APs with eight horizontal APs, are considered.

FIG. 1 illustrates a wireless communication system that may employ a precoding matrix design and periodic channel state information feedback according to some embodiments of the present disclosure. The wireless communication system 100 includes one or more user equipment (UEs), including UE0 explicitly depicted, and one or more base stations (BSs) 101, also referred to a NodeB or evolved NodeB (eNB). UE0 includes an antenna array, a receiver coupled to the antenna array for demodulating received wireless signals, a controller deriving channel quality information, and a transmitter for transmitting feedback to a base station. BS 101 likewise includes at least an antenna array for transmitting and receiving signals, a receiver chain, a controller, and a transmitter chain. In the example shown, UE0 communicates with BS 101 via multiple concurrent streams.

FIG. 1A illustrates a two-row, four-column, cross-polarized, two-dimensional (2D) logical antenna array that may be employed within the wireless communication system of FIG. 1. The 2D logical antenna array comprises N_(col)=4 columns of cross-polarized (x-pol) antenna sub-arrays, wherein each column of x-pol sub-arrays comprises N_(row)=2 pairs of x-pol antennas placed on a substantially vertical line. N_(H) horizontal antenna ports (H-APs) are allocated across the N_(col) columns, where each column of antennas is associated with 2 H-APs respectively for the +45° polarization and for the −45° polarization. For the vertical antenna ports (V-APs), two alternative configurations are explicitly considered in this disclosure: In Option 1, N_(V)=2 V-APs are allocated across the two rows, where each row of antennas is associated with one V-AP. In Option 2, N_(V)=4 V-APs are allocated across the N_(row)=2 rows, where each row of antennas is associated with two V-APs respectively for the +45° polarization and for the −45° polarization.

For PMI feedback for the 2D logical antenna array shown in FIG. 1A, Release-8 N_(V)-Tx CB (Table 1 for N_(V)=2 and Table 2 for N_(V)=4) is used for the vertical CB W_(V) and Release-10 8-Tx inner and outer CBs given in Table 3 and Table 4 are used for the horizontal inner CB W_(1H) and the outer CB W_(2H). The overall codebook can be written as W=W_(V{circle around (×)}W) _(H) with W_(H)=W_(1H)W_(2H), wherein W_(V) is a vertical codebook and W_(H) is the horizontal codebook.

For the PMI feedback for these codebooks, two sets of nonzero-power (NZP) channel-state-information reference-signals (CSI-RS) can be configured via configuration of two parameter sets of {resourceConfig, subframeConfig}. For example, one CSI-RS configuration is provided for estimating W_(H) and the other configuration is provided for estimating W_(V).

In some embodiments, V-PMI is constructed according to one of the following alternatives:

-   -   W_(1V) is the identity matrix and W_(2V) is the precoding matrix         from Release-8 2-Tx codebook, 4-Tx codebook, or a DFT codebook.         In this case, a UE needs to feedback PMI for W_(2V) only; and     -   W_(2V) is the identity matrix and W_(1V) is the precoding matrix         from Release-8 2-Tx codebook, 4-Tx codebook, or a DFT codebook.         In this case, a UE needs to feedback PMI for W_(1V) only.

In some embodiments, the overall rank-1 and rank-2 CB W are constructed as follows, considering that UEs may experience channels in which either elevation or azimuth angle spread is larger than the other.

-   -   A rank-1 codeword w ∈ W is constructed such that both w_(V) ∈         W_(V) and w_(H) ∈ W_(H) are a rank-1 precoding vector.     -   A rank-2 codeword w ∈ W is constructed according to one of the         following methods:         -   w_(V) ∈ W_(V) is a rank-1 precoding vector, and w_(H) ∈             W_(H) is a rank-2 precoding matrix;         -   w_(V) ∈ W_(V) is a rank-2 precoding matrix, and w_(H) ∈             W_(H) is a rank-1 precoding vector.

In this disclosure, the feedback reliability and coverage instead of downlink throughput optimization are placed in the top priority of our PUCCH feedback designs. It is well-known that the payload sizes are directly related to feedback reliability and coverage. Therefore, in this disclosure, payload sizes for respective rank-1 and rank-2 are not increased as compared with those used in Release 10 8-Tx codebook designs.

PUCCH Mode 1-1 Submode 1 for FIG. 1A

In a first design of PUCCH mode 1-1 submode 1 for FIG. 1A, RI and the first H-PMI (W_(1H)) are jointly encoded and are transmitted in the subframes for RI reporting. TABLE 8 lists the details of the joint encoding of RI and W_(1H), with RI=1 or 2. The effective total number of bits for RI+W_(1H) is 5 bits, when eNB is aware of the fact that the maximum rank from a UE is 2. Two design examples of PUCCH mode 1-1 including the other CSI (W_(2V)=W_(V), W_(2H) and CQI) are described below.

TABLE 8 RI and W_(1H) Joint Encoding Total RI RI and W_(1H) joint encoding number bits 1 W_(1H): 0-15 (1^(st) PMI i₁ in Table 3) 4 bits 2 W_(1H): 0-15 (1^(st) PMI i₁ in Table 3) 4 bits Effective total number bits of W_(1H) + RI across ranks 1-2 5 bits

1) PUCCH Mode 1-1 Submode 1 Design 1 for FIG. 1A:

FIG. 2 illustrates a design for PUCCH mode 1-1 submode 1 in accordance with one embodiment of the present disclosure. FIG. 2 illustrates PUCCH mode 1-1 submode 1 Design 1 for FIG. 1A. In those subframes for WB CQI/PMI reporting, WB W_(2H) and WB CQI are transmitted. This design is for cases where reliability requirement of W_(2V) and W_(2H) are the same, and the channels associated with the two PMIs changes in similar time scale. In this and in each of the following examples of subframes reporting CQI and/or PMI on PUCCH, i_(2V) and i_(2H) may be reported in lieu of W_(2V) and W_(2H), respectively, and i_(1V) and i_(1H) may respectively be reported in lieu of W_(1V) and W_(1H). Likewise, discussions below of subsampling any of W_(1V), W_(1H), W_(2V), and W_(2H) for reporting purposes are equally applicable to reporting the corresponding i_(1V), i_(1H), i_(2V) and i_(2H).

TABLE 9 and TABLE 10 contain details of WB (W_(2V), W_(2H))+WB CQI reporting contents respectively for N_(V)=2 and N_(V)=4, in which specific codebook subsampling examples are described.

TABLE 9 (W_(2V), W_(2H)) + WB CQI feedback with 2-Tx V-PMI codebook Total number bits for Total number bits for RI (W_(2V), W_(2H)) (W_(2V), W_(2H)) (W_(2V), W_(2H)) + CQI 1 W_(2V): 0, 2 (CW index of v = 1 of Table 1) 4 bits  8 bits W_(2H): 0-7 (2^(nd) PMI i₂ in Table 3) 2 A first set: 4 bits 11 bits W_(2V): 0, 2 (CW index of v = 1 of Table 1) W_(2H): 0, 1, 4, 5 (2^(nd) PMI i₂ in Table 3) A second set: W_(2V): one of 0, 1, 2 (CW index of v = 2 of Table 1) W_(2H): 0-7 (2^(nd) PMI i₂ in Table 3)

For the case of N_(V)=2 and rank 1, the beam-width in the vertical dimension is fairly wide since only two vertical antenna ports are used. Sub-sampling W_(2V) by a factor of 2 will save additional 1 bit for carrying the information of W_(2H). On the other hand, for W_(2H), it is also proposed to apply sub-sampling in order to keep the payload of (W_(2V), W_(2H)) to be 4 bits so that the reliability of the (W_(2V), W_(2H)) feedback is the same as the legacy W₂+CQI feedback. In the case of N_(V)=2 and rank 2, it is proposed to apply sub-sampling for both W_(2V) and W_(2H) to keep the total payload of (W_(2V), W_(2H))+CQI to be 11 bits, so that PUCCH format 2/2a/2b can carry the information.

In one subsampling example given in TABLE 9, the subsampling set for rank-1 W_(2H) is i₂={0,1,2,3,4,5,6,7}. According to Table 3, both index sets {0,1,2,3} and {4,5,6,7} of the second PMI i₂ respectively corresponds to a first and a second horizontal beams in a codeword W_(1H) with four co-phasing factors {+1, −1, +j, −j}. Sub-sampled W_(2H) only enables horizontal beam selection of beam 1 and beam 2 in a W_(1H) codeword. As W_(1H) is not subsampled, the total number DFT beams can be selected by this particular is W_(2H) subsampling is still 32 in the horizontal dimension of the overall codebook W_(1H)W_(2H), same as that of the Release 10 8-Tx codebook.

One subsampling example for the rank-2 case is also given in TABLE 9. To keep the total number of bits for (W_(2V), W_(2H)) to be 4 bits, only 16 states should be constructed, among which two sets of 8 states are constructed.

-   -   A first set comprises rank-1 W₂, and rank-2 W_(2H). It is         proposed to use {0,2} for rank-1 W_(2V) in Table 1 with υ=1, and         {0,1,4,5} for rank-2 W_(2H). For rank 1 W_(2V), sub-sampling of         a factor 2 is applied. Since the beam-width in the vertical         dimension is relatively wide, sub-sampling of a factor 2 will         not lead to much performance loss. According to Table 4, the         indices 0 and 4 of the second PMI i₂ correspond to the first         horizontal beam in a codeword W_(1H) with co-phasing factors         {+1, −1} and the indices 1 and 5 of the second PMI i₂ correspond         to the second horizontal beam in a codeword W_(1H) with         co-phasing factors {+j, −j}. Sub-sampled W_(2H) enables         horizontal beam selection of only (beam 1, beam 1) and (beam 3,         beam 3) with two sets of co-phasing factors in the rank 2 case.     -   A second set comprises rank-2 W_(2V) and rank-1 W_(2H). In this         case sub-sampling of factor 2 is applied to rank-2 W_(2V). The         index for reporting W_(2V) is fixed to a value among 0, 1, 2,         and no feedback is needed. It is noted that for full-rank         channels, channel capacity does not change over different         choices of orthogonal matrices, and all the three matrices         corresponding to indices 0, 1, 2 are orthogonal. For reporting         rank-1 W_(2H), the subsampling set of W_(2H) in the overall         rank-2 case is chosen to be the same as one in the overall         rank-1 case: {0,1,2,3,4,5,6,7}.

In the case of N_(V)=4, it is proposed to apply sub-sampling for both W_(2V) and W_(2H) to keep the payload of (W_(2V), W_(2H)) to be 4 bits, similarly to the case of N_(V)=2.

In one subsampling example in TABLE 10, the subsampling set for rank-1 W_(2V) is {0,1,2,3} according to the definition in Table 2 with υ=1. The indices 0, 1, 2, and 3 in Table 2 correspond to the four DFT vectors of size 4. The subsampling set for rank-1 W_(2H) is {0,2,8,10}, which are the second PMI in Table 3. The indices 0 and 2 correspond to the selection of beam 1 in the horizontal dimension with respective co-phasing factors 1 and −1, while the indices 4 and 6 correspond to the selection of beam 2 in the horizontal dimension with respective co-phasing factor 1 and −1. Thus, the total DFT beam selection granularity in the horizontal dimension of the overall codebook W_(2V)W_(2H) is the same as that of the Release 10 8-Tx codebook since all the 32 candidate beams are represented. However, unlike the case of N_(V)=2, the co-phasing factors are also sub-sampled by a factor of 2.

TABLE 10 (W_(2V), W_(2H)) and WB CQI feedback with 4-Tx V-PMI codebook Total number bits for Total number bits for RI (W_(2V), W_(2H)) (W_(2V), W_(2H)) (W_(2V), W_(2H)) + CQI 1 W_(2V): 0, 1, 2, 3 (CW index of v = 1 of Table 2) 4 bits  8 bits W_(2H): 0, 2, 4, 6 (2^(nd) PMI i₂ in Table 3) 2 A first set: 4 bits 11 bits W_(2V): 0, 2 (CW index of v = 1 of Table 2) A second set: W_(2H): 0, 1, 2, 3 (2^(nd) PMI i₂ in Table 4) W_(2V): one of 16 CW indices of v = 2 of Table 2 W_(2H): 0-7 (2^(nd) PMI i₂ in Table 3)

One subsampling example for the rank-2 case is also given in TABLE 10. Similarly to the case of N_(V)=2, two sets of 8 states are constructed:

-   -   A first set comprises rank-1 W_(2V) and rank-2 W_(2H). It is         proposed to use {0,2} for rank-1 in Table 2 with υ=1, which         correspond to two DFT vectors of size 4. The selection provides         coarse channel sampling in the vertical dimension. Also it is         proposed to use {0,1,2, and 3} for rank-2 W_(2H). Index sets         {0,1} and {2,3} respectively correspond to the horizontal beam         selection of beam 1 and beam 2 with respective co-phasing factor         sets {+1, −1} and {+1, −1}. By this selection, all possible set         of co-phasing factors are chosen and the total DFT beam         selection granularity in the horizontal dimension is 32 as all         the 32 candidate beams are represented.     -   A second set comprises rank-2 W_(2V) and rank-1 W_(2H). Same as         the N_(V)=2 case, it is proposed to use one value out of those         16 PMI values corresponding to Table 2 with υ=2 for rank-2         W_(2V), similarly to the N_(V)=2 case. For reporting rank-1         W_(2H), the subsampling set is {0,1, . . . , 7} based on the         same reasoning as in the N_(V)=2 case.

2) PUCCH Mode 1-1 Submode 1 Design 2 for FIG. 1A:

FIG. 3 illustrates a second design of PUCCH mode 1-1 submode 1 in accordance with one embodiment of the present disclosure. FIG. 3 illustrates PUCCH mode 1-1 submode 1 Design 2 for FIG. 1A. The reports of the two new reporting types (i.e., WB (W_(2V), W_(2H))+CQI and WB W_(2H) CQI) alternate in time in those subframes for WB CQI/PMI reporting.

TABLE 9 and TABLE 10 are respectively used for (W_(2V), W_(2H)) and WB CQI feedback with N_(V)=2 and N_(V)=4; and TABLE 11 is used for W_(2H) WB CQI. In this design, reliability of H-PMI W_(2H) is improved as compared with Design 1. This is because in every other WB CQI/PMI reporting instances, only the second H-PMI W_(2H) and WB CQI are reported. On the contrary, reliability of V-PMI is reduced as the feedback frequency of the second V-PMI is reduced by half. This reliability reduction may be tolerable in those scenarios where UEs remain more static in the vertical dimension than in the horizontal dimension.

TABLE 11 W_(2H) + CQI feedback Total number Total number RI W_(2H) bits for W_(2H) bits for W_(2H) + CQI 1 W_(2H): 0-15 4 bits  8 bits (2^(nd) PMI i₂ in Table 3) 2 W_(2H): 0-15 4 bits 11 bits (2^(nd) PMI i₂ in Table 4)

3) PUCCH Mode 1-1 Submode 1 Design 3 for FIG. 1A:

FIG. 4 illustrates a third design of PUCCH mode 1-1 submode 1 in accordance with one embodiment of the present disclosure. FIG. 4 illustrates PUCCH mode 1-1 Submode 1 Design 3 for FIG. 1A. In another design of PUCCH mode 1-1 submode 1, RI, W_(2V) (W_(V)) and W_(2H) are jointly encoded and transmitted in RI reporting instances, as illustrated in FIG. 4. Compared to other designs, this design achieves more reliable W_(2H) feedback but less reliability for (W_(2V), W_(1H)) feedback, as the feedback frequency of W_(2V) is reduced and more information, i.e., (W_(2V), W_(1H)), is jointly encoded with RI. Meanwhile, it is proposed to keep the total number of bits for joint encoding RI to be 5, the same as the legacy RI+WB W₁ report. Examples designs of joint encoding of RI and (W_(2V), W_(1H)) are shown in TABLE 12 and TABLE 13, respectively for N_(V)=2 and N_(V)=4.

TABLE 12 Joint encoding of (W_(2V), W_(1H)) + RI with 2-Tx V-PMI codebook Total RI (W_(2V), W_(1H)) number bits 1 W_(2V): 0, 1 (CW index in Table 1 with v = 1) 4 bits W_(1H): 0, 2, 4, 6, 8, 10, 12, 14 (1^(st) PMI i₁ in Table 3) 2 A first set: 4 bits W_(2V): one of 0, 1, 2 (CW index in Table 1 with v = 2) W_(1H): 0, 2, 4, 6, 8, 10, 12, 14 (1^(st) PMI i₁ in Table 4) A second set: W_(2V): 0, 2 (CW index in Table 1 with v = 1) W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) Total number bits of (W_(2V), W_(1H)) + RI across ranks 1-2 5 bits In the overall rank-1 case in TABLE 12, the W_(2V) subsampling set is {0,1} of rank-1 2-Tx codebook and the W_(1H) subsampling set is {0,2,4,6,8,10,12,14}, corresponding to uniformly sampled PMIs in Table 3. By this selection of the subsampling set of W_(1H), the CWs corresponding to the selected PMIs contain all 32 non-overlapping beams.

In the overall rank-2 cases in TABLE 12, it is proposed to the following subsampling for W_(1H) and W_(2V).

-   -   In the case of the rank-2 W_(2V) and the rank-1 W_(1H)         construction, sub-sampling of factor 2 is applied to W_(2V). The         feedback index for W_(2V) is fixed and thus does not need to be         fed back. For the overall rank-2 case, the sub-sampling method         is the same as one in the overall rank-1 case.

In the case of the rank-1 W_(2V) and the rank-2 W_(1H) construction, the W_(2V) subsampling set is {0,2} and the W_(1H) subsampling set is {0,4,8,12}, which selects four codewords with a large spatial separation.

In TABLE 13, the same subsampling method is applied for W_(1H) in the overall rank-1 case as before with the same reasoning. In the overall rank-1 case, the W_(2V) subsampling set is {0,2}. In the case of the overall rank-2 W_(V) and the rank-1 W_(H) construction, the W_(2V) subsampling set is {0,2}. In the case of the rank-1 W_(V) and the rank-2 W_(H) construction, the W_(2V) subsampling set is {0,2}.

TABLE 13 Joint encoding of (W_(2V), W_(1H)) + RI with 4-Tx V-PMI codebook Total RI Sub-sampling for (W_(2V), W_(1H)) number bits 1 W_(2V): 0, 2 (CW index in Table 2 with v = 1) 4 bits W_(1H): 0, 2, 4, 6, 8, 10, 12, 14 (1^(st) PMI i₁ in Table 3) 2 A first set: 4 bits W_(2V): 0, 2 (CW index in Table 2 with v = 2) W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) A second set: W_(2V): 0, 2 (CW index in Table 2 with v = 1) W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) Total number bits of (W_(2V), W_(1H)) + RI across ranks 1-2 5 bits

PUCCH Mode 1-1 Submode 2 for FIG. 1A

In PUCCH Mode 1-1 Submode 2, only RI is transmitted in RI reporting instances.

FIG. 5 illustrates a design for PUCCH mode 1-1 submode 2 in accordance with one embodiment of the present disclosure. FIG. 5 illustrates PUCCH mode 1-1 submode 2 Design 1 for FIG. 1A. In a first design of PUCCH mode 1-1 submode 2, illustrated in FIG. 5, WB (W_(1H), W_(2V))+CQI, and WB (W_(1H), W_(2H))+CQI alternate in time in reporting instances of WB PMI/CQI. In this design, the RI and W_(1H) feedback reliability are the same as those in the legacy 8-Tx codebook. To accommodate additional feedback for W_(2V), the feedback frequency of W_(2H) is reduced.

FIG. 6 illustrates a second design of PUCCH mode 1-1 submode 2 in accordance with one embodiment of the present disclosure. FIG. 6 illustrates PUCCH mode 1-1 Submode 2 Design 2 for FIG. 1A. In a second design of PUCCH mode 1-1 submode 2, illustrated in FIG. 6, WB (W_(1H), W_(2V))+CQI, and WB W_(2H)+CQI alternate in time in WB CQI/PMI reporting instances. Compared with the first design, this design aims to improve the reliability of W_(2H) at the expense of increasing the feedback duty cycle of W_(1H). Since W_(1H) is used to capture long-term and wide-band channel properties, the reduction on the feedback frequency on W_(1H) is not likely to introduce performance degradation.

In these designs, WB (W_(1H), W_(2V))+CQI in TABLE 12 and TABLE 13 can be used respectively for N_(V)=2 and N_(V)=4. TABLE 6 can be used for WB (W_(1H), W_(2H))+CQI, with (W_(1H), W_(2H)) for FIG. 5. TABLE 11 can be used for WB W_(2H) and CQI.

PUCCH Mode 2-1 for FIG. 1A

In PUCCH mode 2-1, reporting type 6 (RI and PTI) are transmitted in RI reporting instances.

1) PUCCH Mode 2-1 Design 1 for FIG. 1A

FIG. 7 illustrates a design for PUCCH mode 2-1 with PTI=0 in accordance with one embodiment of the present disclosure. FIG. 7 illustrates PUCCH mode 2-1 design 1 for FIG. 1A with PTI=0. Referring to FIG. 7 for PTI=0, W_(1H) is transmitted in subframes satisfying the following condition:

-   -   The wideband first precoding matrix indicator report has a         period of H·N_(pd), and is reported on the subframes satisfying         (10×n_(f)+└n_(s)/2┘−N_(OFFSET,CQI))mod(H·N_(pd))=0, where H is         signaled by higher layers.

WB (W_(2V), W_(2H))+CQI are transmitted in those subframes according to the following description:

-   -   Between every two consecutive wideband first precoding matrix         indicator reports, the remaining reporting instances are used         for a wideband second precoding matrix indicator with wideband         CQI.

FIGS. 8A and 8B illustrate two alternative designs of PUCCH mode 2-1 with PTI=1 in accordance with one embodiment of the present disclosure. FIGS. 8A and 8B illustrate PUCCH mode 2-1 Design 1A (FIG. 8A) and Design 1B (FIG. 8B) for FIG. 1A with PTI=1. In FIGS. 8A and 8B for PTI=1, WB (W_(2V), W_(2H))+WB CQI are transmitted in reporting instances of WB CQI/PMI.

Either SB (W_(2V), W_(2H))+CQI or SB W_(2H) CQI are transmitted according to the following description:

-   -   Between every two wideband CQI/wideband second PMI reports, the         remaining J·K reporting instances are used in sequence for         subband CQI reports on K full cycles of bandwidth parts except         when the gap between two consecutive wideband CQI/PMI reports         contains less than J·K reporting instances due to a system frame         number transition to 0, in which case the UE shall not transmit         the remainder of the subband CQI reports which have not been         transmitted before the second of the two wideband CQI/wideband         second PMI reports. Each full cycle of bandwidth parts shall be         in increasing order starting from bandwidth part 0 to bandwidth         part J−1. The parameter K is configured by higher-layer         signaling.

TABLE 14 and TABLE 15 show design examples for WB (W_(2V), W_(2H))+CQI, and SB (W_(2V), W_(2H))+CQI respectively for N_(V)=2 and N_(V)=4. In particular, the sub-sampling methods for WB (W_(2V), W_(2H))+CQI in TABLE 14 and TABLE 15 are identical to those for WB (W_(2V), W_(2H)) and WB CQI in TABLE 9 and TABLE 10. SB (W_(2V), W_(2H)) is obtained by further sub-sampling WB (W_(2V), W_(2H)) as given in TABLE 14 and TABLE 15. Hence, at the sub-band level, PUCCH feedback is coarser than that for WB.

TABLE 14 WB (W_(2V), W_(2H)) + CQI and SB (W_(2V), W_(2H)) + CQI (N_(V) = 2) Total number bits Total number bits RI (W_(2V), W_(2H)) (W_(2V), W_(2H)) (W_(2V), W_(2H)) + CQI 1 WB W_(2V): 0, 2 (CW index in Table 1 with v = 1) 4 bits    8 bits WB W_(2H): 0-7 (2^(nd) PMI i₂ in Table 3) 1 SB W_(2V): 0, 2 (CW index in Table 1 with v = 1) 4 bits 8 + L bits SB W_(2H): 0-7 (2^(nd) PMI i₂ in Table 3) (8 + subband selection) 2 A first set: 4 bits   11 bits WB W_(2V): 0, 2 (CW index in Table 1 with v = 1) WB W_(2H): 0, 1, 4, 5 (2^(nd) PMI i₂ in Table 4) A second set: WB W_(2V): one of 0, 1, 2 (CW index in Table 2 with v = 2) WB W_(2H): 0-7 (2^(nd) PMI i₂ in Table 3) 2 A first set: 2 bits 9 + L bits SB W_(2V): one of 0, 1, 2, 3 (CW index in Table 2 with v = 1) SB W_(2H): 0, 4 (2^(nd) PMI i₂ in Table 4) A second set: WB W_(2V): one of 0, 1, 2, 3 (CW index in Table 2 with v = 2) SB W_(2H): 0, 4 (2^(nd) PMI i₂ in Table 3)

TABLE 15 WB (W_(2V), W_(2H)) + CQI and SB (W_(2V), W_(2H)) + CQI (N_(V) = 4) Subsampling for WB (W_(2V), W_(2H)) Total Total number bits RI and SB (W_(2V), W_(2H)) number bits (W_(2V), W_(2H)) + CQI 1 WB W_(2V): 0, 1, 2, 3 (CW index in Table 2 with v = 1) 4 bits    8 bits WB W_(2H): 0, 2, 8, 10 (2^(nd) PMI i₂ in Table 3) 1 SB W_(2V): 0, 1, 2, 3 (CW index in Table 2 with v = 1) 4 bits 8 + L bits SB W_(2H): 0, 2, 8, 10 (2^(nd) PMI i₂ in Table 3) (8 + subband selection) 2 A first set: 4 bits   11 bits WB W_(2V): 0, 2 (CW index in Table 2 with v = 1) WB W_(2H): 0, 1, 4, 5 (2^(nd) PMI i₂ in Table 4) A second set: WB W_(2V): one of 16 CW indices in Table 2 with v = 2 WB W_(2H): 0-7 (2^(nd) PMI i₂ in Table 4) 2 A first set: 2 bits 9 + L bits SB W_(2V): one of 16 CW indices in Table 2 with v = 1 SB W_(2H): 0, 4 (2^(nd) PMI i₂ in Table 4) A second set: WB W_(2V): one of 16 CW indices in Table 2 with v = 2 SB W_(2H): 0, 4 (2^(nd) PMI i₂ in Table 4)

Regarding SB W_(2H)+CQI feedback, TABLE 7 can be used for codebook subsampling. By limiting the SB feedback only on W_(2H), this design achieves better protection of the feedback W_(2H) information than the other SB feedback design in FIG. 8.

2) PUCCH Mode 2-1 for FIG. 1A Design 2

FIG. 9 illustrates another design for PUCCH mode 2-1 with PTI=0 in accordance with one embodiment of the present disclosure. FIG. 9 illustrates PUCCH mode 2-1 Design 2 for FIG. 1A with PTI=0. In FIG. 9 for PTI=0, W_(1H) is transmitted in the same subframes as those for W_(1H) transmission in FIG. 7. WB (W_(2V), W_(2H))+WB CQI and WB W_(2H)+CQI alternate in time in those subframes for reporting WB (W_(2V), W_(2H))+CQI in FIG. 7.

FIG. 10 illustrates another design for PUCCH mode 2-1 with PTI=1 in accordance with one embodiment of the present disclosure. FIG. 10 illustrates PUCCH mode 2-1 Design 2 for FIG. 1A with PTI=1. In FIG. 10 for PTI=1, WB (W_(2V), W_(2H))+CQI are transmitted in reporting instances of WB CQI/PMI. SB (W_(2V), W_(2H))+CQI, WB W_(2H)+CQI, and SB W_(2H)+CQI take turns in time in the same subframes as those for FIG. 8. TABLE 14 and TABLE 15 can be used for sub-sampling for WB (W_(2V), W_(2H))+CQI, and SB (W_(2V), W_(2H))+CQI, respectively for N_(V)=2 and N_(V)=4.

In this design option, the reliability of W_(2H) is improved as compared with design option 1 since sometimes only W_(2H)+CQI are transmitted. However, since the feedback frequency of W_(2V) is larger than that in option 1, the reliability of W_(2V) decreases. As discussed earlier, UEs can be more static in the vertical dimension than the horizontal dimension in some scenarios. The reduction on W_(2V) by half may only cause marginal performance degradation.

FIG. 1B illustrates a four-row, four-column, cross-polarized, two-dimensional logical antenna array that may be employed within the wireless communication system of FIG. 1. The 2D logical antenna port array of FIG. 1B comprises N_(col)=4 columns of cross-polarized (x-pol) antenna sub-arrays, wherein each column of x-pol sub-arrays comprises N_(row)=4 sets of x-pol antenna elements. Although FIG. 1B has specific number of rows and columns, the embodiments associated with FIG. 1B can be used for any arbitrary number of rows and columns.

In some embodiments, the 32 antenna ports in FIG. 1B are indexed as A(r, 0), A(r, 1), . . . , A(r, 7), A(1,0), wherein r=0, 1, 2, 3 and A(r, 0), A(r, 1), . . . , A(r, 7) are for 8 antenna ports in a r-th row. Correspondingly, a UE is configured with N_(row) sets of CSI-RS: a first set comprising A(0,0), A(0,1), . . . , A(0,7); and a second set comprising A(1,0), A(1,1), . . . , A(1,7). Correspondingly, UE is configured with N_(row) parameter sets of {resourceConfig, subframeConfig}, which specifies the time-frequency location of the N_(row) sets of NZP CSI-RS.

In some embodiments, the 32 antenna ports in FIG. 1B are indexed with A0,A1,A2, . . . , A31, wherein positive integers are sequentially assigned starting from 1 along the elements in a first row, and then continuously increase along the elements in a second row, etc. Correspondingly, a UE is configured with one set of CSI-RS A0,A1,A2, . . . , A31.

In some embodiments, out of the 32 antenna ports in FIG. 1B, 8 antenna ports in a first row are indexed with H0,H1, . . . , H7, the assigned numbers wherein non-negative integers are sequentially assigned starting from 0 along the elements with a first polarization in a first row and then along the elements with a second polarization in the first row.

In some embodiments, out of the 32 antenna ports in FIG. 1B, 4 antenna ports with a same polarization in a first column are indexed with H0, H1,H2,H3.

In some embodiments, out of the 16 antenna ports in FIG. 1B, 4 antenna ports in a first column are indexed with V0,V1, . . . , V7, wherein V0,V1, V2 and V3 are with a first polarization and V4,V5,V6 and V7 are with a second polarization.

In some embodiments, a UE is configured to report horizontal-channel PMI (H-PMI) and vertical channel PMI (V-PMI), wherein H-PMI and V-PMI represent a precoding matrix respectively in azimuth and elevation domains. The precoding matrices corresponding to H-PMI and V-PMI are respectively referred to as H and V precoding matrix (or vector).

For facilitating H-PMI and V-PMI feedback, the UE is configured with N parameter sets of {resourceConfig, subframeConfig}, which specifies the time-frequency location of N groups of nonzero-power (NZP) channel-state-information reference-signals (CSI-RS), wherein the antenna ports associated with CSI-RS can be constructed according to some embodiments of the current disclosure.

In one example, one group of CSI-RS is provided for estimating W_(H) and the other is provided for estimating W_(V).

FIG. 1C illustrates logical port to antenna port mapping that may be employed within the wireless communication system of FIG. 1 according to some embodiments of the current disclosure. In the figure, transmission (Tx) signals on each logical port is fed into an antenna virtualization matrix (e.g., of a size M×1), output signals of which are into a set of M physical antenna ports. In some embodiments, M corresponds to a total number of antenna elements on a substantially vertical axis. In some embodiments, M corresponds to a ratio of a total number of antenna elements to a variable S, on a substantially vertical axis, wherein M and S are each chosen to be a positive integer.

In some embodiments, both vertical and horizontal codebooks (W_(H) and W_(V)) have double codebook structure: the codebooks W_(H) and W_(V) are such that W_(H)=W_(1H)W_(2H) and W_(V)=W_(2V)W_(2V), wherein Release-10 8-Tx inner CB in Table 3 is used both for the vertical inner CB W_(1V) and the horizontal inner CB W_(1H).

Inner Codebook W₁

In some embodiments, the vertical and horizontal inner codebooks W_(1V) and W_(1H) can be expressed as a block diagonal matrix defined as follows:

${W_{1V} = \left\{ {\begin{matrix} {X_{V}\left( i_{1V} \right)} & 0 \\ 0 & {X_{V}\left( i_{1V} \right)} \end{matrix},{i_{1V} = 0},1,\ldots \mspace{14mu},15} \right\}},{W_{1H} = \left\{ {\begin{matrix} {X_{H}\left( i_{1H} \right)} & 0 \\ 0 & {X_{H}\left( i_{1H} \right)} \end{matrix},{i_{1H} = 0},1,\ldots \mspace{14mu},15} \right\}},$

where W_(1V) and W_(1H) are selected to be a 4×4 matrix X(i) defined as in the following:

X(i)

[ν_(2imod32) ν_((2i+1)mod32) ν_((2i+2)mod32) ν_((2i+3)mod32)]

with ν_(n)=[1 e^(j2πn/32) e^(j2π2n/32) e^(j2π3n/32)]^(T) and with i=0,1, . . . , 15.

Then, the composite inner codebook W₁ is constructed as follows:

$W_{1} = \begin{Bmatrix} {{X_{V}\left( i_{1V} \right)} \circ {X_{H}\left( i_{1H} \right)}} & 0 \\ 0 & {{X_{V}\left( i_{1V} \right)} \circ {X_{H}\left( i_{1H} \right)}} \end{Bmatrix}$

where the operator ∘ denotes the column-wise Kronecker product of two matrices, also called the Khatri-Rao product, and where W₁ can therefore be rewritten as:

W ₁=[ν_(2i) _(1V) _(mod32)

ν_(2i) _(1H) _(mod32)

ν_((2i) _(1H) _(+1)mod32) . . . ν_((2i) _(1V) _(+3)mod32)

ν_((2i) _(1H) _(+3)mod32)].

Here, the matrix X_(V) (i_(1V))∘X_(H)(i_(1H)) consists of 16 beams of size 16×1, wherein the 16 beams are all of the Kronecker product of the 4-H and the 4 V-beams. Hence, the size of the FD-MIMO inner codebook matrix W₁ is 32×32. The number of distinct W₁ codewords is 256 and the number of bits for W₁ is 8 bits.

Outer Codebook W₂

In some embodiments, W₂ is constructed as in the following. Define e_(i) as a 16×1 column vector whose entries are all zero except for the i-th entry being 1. For Rank 1, the codebook (precoding matrix) W₂ is given by

${W_{2} = \begin{Bmatrix} \begin{bmatrix} Y_{1} \\ Y_{1} \end{bmatrix} & \begin{bmatrix} Y_{1} \\ {- Y_{1}} \end{bmatrix} & \begin{bmatrix} Y_{1} \\ {j\; Y_{1}} \end{bmatrix} & \begin{bmatrix} Y_{1} \\ {{- j}\; Y_{1}} \end{bmatrix} \end{Bmatrix}},$

where Y₁ ∈ {e₁ e₂ . . . e₁₆} corresponds to the beam selection. The size of the outer codebook W₂ is 16×4=64 (6 bits). For each codeword in W₂, the beam selection index i for i=1,2, . . . , 16 can be decomposed into two indices (m, m′) with i=4m+m′+1, where m is the vertical beam selection index with 0≦m≦3 and m′ is the horizontal beam selection index with 0≦m′≦3. TABLE 16 shows the mappings between beam selection vectors e_(i) (or index i) and the vertical beam selection index m and the horizontal beam selection index m′, respectively. Each Y₁ ∈ {e₁ e₂ . . . e₁₆} is mapped onto a unique pair of (m, m′) according to TABLE 16. In the rank-1 case, the co-phasing factor denoted by φ_(n) is e^(jπn/2), for n=0,1,2,3.

TABLE 16 Mapping between the beam selection vector e_(i) and the horizontal and vertical beam selection indices m and m′ Beam selection vector e_(i) e₁ e₂ e₃ e₄ e₅ e₆ e₇ e₈ e₉ e₁₀₁ e₁₁ e₁₂ e₁₃ e₁₄ e₁₅ e₁₆ m index 0 0 0 0 1 1 1 1 2 2 2 2 3 3 3 3 m′ index 0 1 2 3 0 1 2 3 0 1 2 3 0 1 2 3

For W₂, the beam selection indices m and m′, and co-phasing factors φ_(n) are determined by two indices, namely, i_(2V) and i_(2H). TABLE 17 illustrates one method to map i_(2V) and i_(2H) to m, m′ and n in the rank-1 case. The vertical beam selection index m is indicated by i_(2V). The horizontal beam selection index m′ and co-phasing factors {+1, −1, +j, −j} (4 states) are jointly encoded and indicated by i_(2H).

TABLE 17 i_(2V) and i_(2H) mapping (Rank 1) i_(2V) indices m i_(2H) indices {m′, n} 0 0 0, 1, 2, 3 {0, 0} {0, 1} {0, 2} {0, 3} 1 1 4, 5, 6, 7 {1, 0} {1, 1} {1, 2} {1, 3} 2 2 8, 9, 10, 11 {2, 0} {2, 1} {2, 2} {2, 3} 3 3 12, 13, 14, 15 {3, 0} {3, 1} {3, 2} {3, 3}

TABLE 18 clarifies the mapping from composite PMI (i_(1V), i_(1H), i_(2V), i_(2H)) to m, m′ and n, wherein the first V-PMI i_(1V)={0, . . . , 15}, the second V-PMI i_(2V)={0, . . . , 3}, the first H-PMI i_(1H)={0, . . . , 15}, and the second H-PMI i_(2H)={0, . . . , 15}.

In some embodiments, the precoding vector to derive rank-1 CQI is constructed by:

${w_{m,m^{\prime},n} = {\frac{1}{\sqrt{32}}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} \end{bmatrix}}},$

wherein ν_(m) is a first precoding vector selected from a first codebook, ν_(m′) is a second precoding vector selected from a second codebook, and φ_(n) is a co-phase.

In one example, the first codebook for ν_(m) is an N₁-Tx DFT codebook oversampled with oversampling factor o₁ and the second codebook for ν_(m′) is an N₂-Tx DFT codebook oversampled with oversampling factor o₂.

In one method, a UE is configured to report information regarding m, m′, and n.

In one example, m, m′, and n are determined according to TABLE 17 and equivalently according to TABLE 18, and the UE is configured to report one or more of i_(1V), i_(1H), i_(2V), and i_(2H).

TABLE 18 Codebook for 1-layer CSI Reporting i_(2H) 0 1 2 3 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,3) 4 5 6 7 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,3) 8 9 10 11 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,3) 12 13 14 15 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,3) $w_{m,m^{\prime},n} = {\frac{1}{\sqrt{32}}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} \end{bmatrix}}$

For a given pair of (i_(1V), i_(2V)), w_(m,m′n) is constructed by the indices (i_(1H), i_(2H)) in the same manner as TABLE 4. The indices m, m′ and n are employed to select the (rank-1) precoding matrix that includes a first column comprising a first row partition and a second row partition, the first row partition containing (as indicated by the formula in TABLE 18] a Kronecker product of at least first and second precoding vectors ν_(m) and ν_(m′) and the second row partition containing a Kronecker product of a first term (the product of a co-phasing factor φ_(n) and the first precoding vector ν_(m)) and a second term (the second precoding vector ν_(m′)). As discussed above, the first precoding vector ν_(m) is selected from a first codebook and the second precoding vector ν_(m′) is selected from a second codebook. It is noted that the roles of H and V in these embodiments can be swapped, without departing from the principles of the current disclosure.

In some embodiments, when the UE is configured with TABLE 3 or TABLE 17 for W_(2H) (or i_(2H)) feedback, subsampling of W_(2H) is {0,2,4,6,8,10,12,14} when the most recently reported RI is 1, in which case all the four beams with two co-phasing factors {0, π} are selected. The number of beams is used to provide the long-term wideband coverage for UEs while the co-phasing factors are used to adjust beams to be adaptive the short-term frequency selectivity of the channel. Hence, more bits are allocated to beam selection indices than the co-phasing factors.

In some embodiments, when the UE is configured with TABLE 3 or TABLE 17 for W_(2H) (or i_(2H)) feedback, subsampling of W_(2H) is {0,2,4,6,8,10,12,14} when the most recently reported RI is 1, in which case all the four co-phasing factors corresponding to a first and a second beam indices are selected. As the DFT beams are already over-sampled, losing the two beam indices is not likely to introduce significant performance loss.

In some embodiments, eNB transmits two data streams to a UE along two different spatial directions on the same time-frequency resource. In order for the UE to help eNB's determine these two directions for the DL transmissions, the UE reports a rank-2 PMI indicating a composite rank-2 precoding matrix comprising two column vectors, wherein each column vector is associated with a direction whose signal path is strong for the UE. Each column vector can be represented by a Kronecker product of horizontal and vertical (or azimuth and elevation) precoding vectors. In some scenarios, angle spread in elevation domain is much smaller than angle spread in azimuth domain; in some other scenarios, angle spread in azimuth domain is much smaller than angle spread in elevation domain.

In one example scenario where elevation spread is much smaller than azimuth spread, a UE is likely to receive best rank-2 beams in a horizontal plane. When the most recently reported rank is 2 (RI=2), it is proposed that the UE should report rank-2 PMI corresponding to a composite rank-2 precoding matrix constructed by a Kronecker product of a rank-2 H precoding matrix and a rank-1 V precoding vector. It is noted that the role of H and V in these embodiments can be swapped without departing from the principles of the current disclosure.

In some embodiments, for rank-2, the codebook (precoding matrix) W₂ is constructed by

${W_{2} = \begin{bmatrix} Y_{1} & Y_{2} \\ {\phi_{n}Y_{1}} & {{- \phi_{n}}Y_{2}} \end{bmatrix}},$

wherein (Y₁, Y₂)=(e_(i1), e_(i2)). For a selected (Y₁, Y₂) pair, two rank-2 co-phasing factors φ_(n) can be selected, either φ_(n)=1 or j.

In some embodiments, a UE can be configured to report rank-2 PMI, wherein the rank-2 PMI indicates a constant direction (or precoding vector) in either of azimuth or elevation domain and two directions (or two precoding vectors) in the other domain.

For example, eNB may configure a UE to report rank-2 PMI, wherein a common beam selection index m is used for constructing a vertical precoding vector, and two separate beam selection indices m′, m″ are used for constructing the two horizontal precoding vectors, wherein the composite precoding matrix is constructed by taking Kronecker product of the vertical precoding vector and each of the two horizontal precoding vectors. In this case, (Y₁, Y₂)=(e_(i1), e_(i2)) can be determined i₁=4m+m′+1 and i₂=4m+m″+1. In this case, eNB may utilize channel-reciprocity channel estimation based upon uplink signal estimation, to figure out such a channel condition.

A similar example can be constructed for the case where azimuth domain channel spread is smaller than elevation domain spread, in which case a UE is configured to feed back a common beam selection index for a horizontal precoding vector, and two beam selection indices for two vertical precoding vectors.

In some embodiments, (i_(2V), i_(2H)) are mapped to m, m′, m″ and n, wherein vertical beam selection index m is mapped by i_(2V) and two horizontal beam selection indices (m′, m″) and the co-phasing factor index n are jointly indicated by i_(2H), wherein i_(2V)={0, . . . , 3} and i_(2H)={0, . . . , 15}. In this case, for a given second V-PMI i_(2V), the second H-PMI i_(2H) maps to a rank-2 precoding matrix according to Rel-10 rank-2 codebook table, i.e., TABLE 4. Hence, in order to calculate and report H-PMI, most of the legacy UE implementation deriving 8-Tx PMI can be used.

In some embodiments (i_(2V), i_(2H)) are mapped to m, m′, m″ and n, wherein vertical beam selection index m is mapped by i_(2V) and two horizontal beam selection indices (m′, m″) and the co-phasing factor index n are jointly indicated by i_(2H), wherein i_(2V)={0, . . . , 7} and i_(2H)={0, . . . , 7}. In this case, for both second V-PMI i_(2V) and second H-PMI i_(2H), feedback payload size is the same, which is 3 bits. This design enables that the two PUCCH reports respectively comprising i_(2V) and i_(2H) are received with same reliability.

In some embodiments, for rank 2 the codebook (precoding matrix) W₂ is given by

${W_{2} = \begin{matrix} \begin{bmatrix} Y_{1} & Y_{2} \\ Y_{1} & {- Y_{2}} \end{bmatrix} & \begin{bmatrix} Y_{1} & Y_{2} \\ {j\; Y_{1}} & {{- j}\; Y_{2}} \end{bmatrix} \end{matrix}},$

where (Y₁, Y₂)∈ {(e_(i), e_(i)): i=1, . . . , 16} ∪ {(e_(l), e_(l+1)), (e_(l+1), e_(l+2)), (e_(l), e_(l+3)), (e_(l+1), e_(l+3)), l=1,5,9,10}. According to this construction, (Y₁, Y₂) can have 32 different values, wherein all four different vertical beams indicated by i_(1V) can be selected, and for a given selected vertical beam, 8 pairs of horizontal beams can be selected to comprise two beams for 8 rank-2 precoding matrices.

TABLE 19 lists 32 selected pairs of beam selection indices for this CB construction in the rank 2 case, in which shaded regions are used to indicate selected beam index pairs. According to TABLE 19, with referring to TABLE 16, for each rank-2 precoding matrix a single vertical beam selection index m and two horizontal beam selection indices m′ and m″ are used. Each (Y₁, Y₂) located in the same block diagonal box has the same vertical beam selection index.

TABLE 19 The 32 pairs of the beam selection indices in CB (Rank = 2)

TABLE 20 illustrates a mapping from (i_(2V), i_(2H)) to m, m′, m″ and n according to some embodiments of the present disclosure, wherein vertical beam selection index m (2 bits) is mapped by i_(2V) and horizontal beam selection indices (m′, m″) and the co-phasing factor index n are jointly indicated by i_(2H).

TABLE 20 i_(2V) and i_(2H) mapping method (Rank 2) i_(2V) CW indices m i_(2H) CW indices (m′, m″, n) 0 0 0, 1, 2, 3 (0, 0, 0) (0, 0, 1) (1, 1, 0) (1, 1, 1) 1 1 4, 5, 6, 7 (2, 2, 0) (2, 2, 1) (3, 3, 0) (3, 3, 1) 2 2 8, 9, 10, 11 (0, 1, 0) (0, 1, 1) (1, 2, 0) (1, 2, 1) 3 3 12, 13, 14, 15 (0, 3, 0) (0, 3, 1) (1, 3, 0) (1, 3, 1)

TABLE 21 clarifies the mapping from composite PMI (i_(1V), i_(1H), i_(2V), i_(2H)) to m, m′, m″ and n, wherein the first V-PMI i_(2V)={0, . . . , 15}, the second V-PMI i_(2V)={0, . . . , 3}, the first H-PMI i_(1H)={0, . . . , 15}, and the second H-PMI i_(2H)={0, . . . , 15}.

In some embodiments, the precoding vector used for deriving rank-2 CQI is constructed by:

${W_{m,m^{\prime},m^{\prime\prime},n}^{(2)} = {\frac{1}{8}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{\prime\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{\prime\prime}}}} \end{bmatrix}}},$

wherein ν_(m) is a first precoding vector selected from a first codebook, ν_(m′) and ν_(m″) are a second and a third precoding vector selected from a second codebook, and φ_(n) is a co-phase.

In one example, the first codebook for ν_(m) is an N₁-Tx DFT codebook oversampled with oversampling factor o₁ and the second codebook for ν_(m′) and ν_(m″) is an N₂-Tx DFT codebook oversampled with oversampling factor o₂.

In one method, a UE is configured to report information regarding m, m′, m″, and n.

In one example, m, m′, m″ and n are determined according to TABLE 17, and equivalent according to TABLE 21, and UE is configured to report i_(1V), i_(1H), i_(2V), and i_(2H).

TABLE 21 Codebook for 2-layer CSI Reporting i_(2H) 0 1 2 3 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+1,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+1,1) 4 5 6 7 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,2i) _(1H) _(+2,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,2i) _(1H) _(+2,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,2i) _(1H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,2i) _(1H) _(+3,1) 8 9 10 11 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(+1,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(+1,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+2,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+2,1) 12 13 14 15 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(2H) _(,2i) _(2H) _(+3,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(2H) _(+1,2i) _(2H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(2H) _(+1,2i) _(2H) _(+3,1) $w_{m,m^{\prime},m^{''},n} = {\frac{1}{8}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{''}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{''}}}} \end{bmatrix}}$

In some embodiments, for the rank-2 case, when the UE is configured with TABLE 20 for W_(2H) (or i_(2H)) feedback, subsampling of W_(2H) is {0,2,4,6,8,10,12,14} when the most recently reported RI is 2, in which case all the eight beam selection pairs and a single co-phasing factor are chosen. The rationale behind such choices is that the number of beam selection pairs could be more crucial for the rank-2 beamforming performance.

In some embodiments, for the rank-2 case, when the UE is configured with TABLE 20 for W_(2H) (or i_(2H)) feedback, subsampling of W_(2H) is {0,1, 2, 3, 4, 5, 6, 7} when the most recently reported RI is 2, in which case four beam selection pairs with the same beams and both co-phasing factors are chosen. The rationale behind such choices is that the number of co-phasing factors could be more crucial for the rank-2 beamforming performance.

TABLE 22 illustrates a mapping from (i_(2V), i_(2H)) to m, m′, m″ and n according to some embodiments of the present disclosure, wherein vertical beam selection index m (2 bits) and co-phasing factor index n are mapped by i_(2V) and horizontal beam selection indices (m′, m″) are jointly indicated by i_(2H). Here the first V-PMI is i_(1V)={0, . . . , 15}, the second V-PMI is i_(2V)={0, . . . , 7}, the first H-PMI is i_(1H)={0, . . . , 15}, and the second H-PMI is i_(2H)={0, . . . , 7}. The precoding matrix used for deriving rank-2 CQI is constructed by

$W_{m,m^{\prime},m^{\prime\prime},n}^{(2)} = {{\frac{1}{8}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{\prime\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{\prime\prime}}}} \end{bmatrix}}.}$

TABLE 22 i_(2V) and i_(2H) mapping method (Rank 2) i_(2V) indices (m, n) i_(2H) indices (m′, m″) 0 (0, 0) 0 (0, 0) 1 (0, 1) 1 (1, 1) 2 (1, 0) 2 (2, 2) 3 (1, 1) 3 (3, 3) 4 (2, 0) 4 (0, 1) 5 (2, 1) 5 (1, 2) 6 (3, 0) 6 (0, 3) 7 (3, 1) 7 (3, 0)

PUCCH Mode 1-1 Submode 1

FIG. 11 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure, when the UE is configured with PUCCH mode 1-1 submode 1. In RI reporting instances, RI and (W_(1V), W_(1H)) are jointly encoded and are transmitted. In CQI/PMI reporting instances, WB (W_(2V), W_(2H))+CQI are transmitted. In this design, W_(1V) and W_(2V) are respectively transmitted together with W_(2H) and W_(2H), and hence the overall PMI decoding reliability may get degraded if full PMI is transmitted for V- and H-PMI.

In some embodiments, a UE is configured to select and report W_(1V), which is selected from a subsampled set out of 0, 1, . . . , 15, in order to keep the payload of a PUCCH report small, such that the decoding reliability is good. In one method, uniform subsampling is applied; for example, when the subsampling set size is 4, the subsampled values are {0, 4, 8,12}.

In some embodiments, W_(1V) is subsampled such that typical values for zenith angle of departure (ZoD) are still kept in the subsampled set. When a UE is on the ground plane and the UE-BS distance is far enough, the zenith angle of departure (θ) converges to 90°. Therefore it is important to keep a PMI index representing θ=90°, which corresponds to i_(1V)=0. On the other hand, in typical macro scenarios, base stations are above UEs on the average, and hence, it would be important to represent those zenith angles well above 90°, e.g., 120°. When ZoD is θ, optimal beam steering angle ν is determined by

$v = {\frac{2\pi \; d_{V}}{\lambda_{c}}\cos \mspace{11mu} {\theta_{0}.}}$

On the other hand, a first DFT beam angle corresponding to W_(1V) (i_(1V)) is

$\frac{2\pi \; i_{1V}}{32}.$

Then, given i_(1V)=0, 4, 8, 12, corresponding ZoD's can be obtained as shown in TABLE 23.

TABLE 23 ZoD angles corresponding to W1V PMI A first DFT beam angle W_(1V) (i_(1V)) (2πi_(1V)/32) θ with d_(V) = 0.5λ θ with d_(V) = λ 0 0 π/2 (90°) π/2 (90°) 4 π/2 π/3 (120°) 1.32 (108°) 8 π 0 (0°) π/3 (120°) 12 3π/2 = −π/2 2π/3 (60°) 0.72 (139°)

In one method, {0, 4} is used as the subsampled values of W_(1V). In another method, {0, 8} is used as the subsampled values of W_(1V). In another method, the subsampled values of include 0 and x, wherein x ∈ {0, 1, 2, . . . , 15} is configured by higher-layer.

TABLE 24 illustrates a method to jointly encode of RI and (W_(1V), W_(1H)) according to some embodiments of the present disclosure. For the vertical and the horizontal W₁ feedback, uniform subsampling is applied with a same subsampling factor, which is 4, in order to keep the payload small so that the joint feedback can be reliably received at the eNB.

TABLE 24 RI and (W_(1V), W_(1H)) Joint Encoding RI RI and (W_(1V), W_(1H)) joint encoding Total number bits 1 W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) 4 bits W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) 2 W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) 4 bits W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) Total number bits of RI + (W_(1V), W_(1H)) 5 bits for ranks 1-2

TABLE 25 illustrates another method to jointly encode of RI and (W_(1V), W_(1H)) according to some embodiments of the present disclosure. For the horizontal W₁ feedback, uniform subsampling is applied with subsampling factor 2; on the other hand for the vertical W₁ feedback, two indices are carefully chosen such that the elevation angles found in typical deployment scenarios are well represented.

TABLE 25 RI and (W_(1V), W_(1H)) Joint Encoding Method 2 Total number RI RI and (W_(1V), W_(1H)) joint encoding bits 1 W_(1V): 0, 8 (1^(st) PMI i₁ in Table 3) 4 bits W_(1H): 0, 2, 4, 6, 8, 10, 12, 14 (1^(st) PMI i₁ in Table 3) 2 W_(1V): 0, 8 (1^(st) PMI i₁ in Table 4) 4 bits W_(1H): 0, 2, 4, 6, 8, 10, 12, 14 (1^(st) PMI i₁ in Table 4) Total number bits of the joint codebook RI + 5 bits (M_(1V), W_(1H)) for ranks 1-2

TABLE 26 illustrates a method to encode (W_(2V), W_(2H)) and WB CQI feedback according to some embodiments of the present disclosure.

TABLE 26 (W_(2V), W_(2H)) and WB CQI feedback Total Total number number bits for bits for (W_(2V), W_(2H)) + RI (W_(2V), W_(2H)) (W_(2V), W_(2H)) CQI 1 W_(2V): 0, 2 (i_(2V) CW index in Table 8) 4 bits 8 bits W_(2H): 0, 2, 4, 6, 8, 10, 12, 14 (i_(2H) CW index in Table 8) 2 Option 1: 4 bits 11 bits W_(2V): 0, 2 (i_(2V) CW index in Table 11) W_(2H): 0-7 (i_(2H) CW index in Table 11) Option 2: W_(2V): 0, 2, 4, 6 (i_(2V) CW in Table 13) W_(2H): 0-3 (i_(2H) CW in Table 13)

1) PUCCH Mode 1-1 Submode 1 Design 2 for FIG. 1B:

FIG. 12 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure, when the UE is configured with PUCCH mode 1-1 submode 1. FIG. 12 PUCCH mode 1-1 submode 1 for FIG. 1B. In this design, WB W_(2V)+CQI and WB W_(2H)+CQI reports alternate in time in WB CQI/PMI reporting instances. Although feedback frequency of W_(2V) and W_(2H) is effectively reduced in this design, subsampling is not necessary, which ensures better decoding reliability at the receiver side.

A design for WB W_(2V)+CQI and WB W_(2H)+CQI can be respectively found in TABLE 27 and TABLE 28.

TABLE 27 WB W_(2V) + CQI Total Total number number bits for bits for RI W_(2V) + CQI W_(2V) W_(2V) + CQI 1 W_(2V): 0-3 (i_(2V) CW index in Table 8) 2 bits 6 bits 2 Option 1: 2 bits 9 bits W_(2V): 0-3 (i_(2V) CW index in Table 11) Option 2: 3 bits 10 bits  W_(2V): 0-7 (i_(2V) CW in Table 13)

TABLE 28 WB W_(2H) + WB CQI Total number Total number bits for bits for RI W_(2H) + CQI W_(2H) W_(2H) + CQI 1 W_(2H): 0-15 (i_(2H) CW index in Table 8) 4 bits 6 bits 2 Option 1: 3 bits 10 bits W_(2H): 0, 2, 4, 6, 8, 10, 12, 14 (i_(2H) CW index in Table 11) Option 2: W_(2H): 0-7 (i_(2H) CW in Table 13)

PUCCH Mode 1-1 Submode 2

In PUCCH mode 1-1 submode 2, only RI is transmitted in RI reporting instances.

FIG. 13 illustrates PUCCH feedback over multiple subframes according to some embodiments of the present disclosure, when the UE is configured with PUCCH mode 1-1 submode 2, wherein WB (W_(1V), W_(2V))+CQI and WB (W_(1H), W_(2H))+CQI alternate in time in WB PMI/CQI reporting instances. FIG. 13 illustrates PUCCH mode 1-1 Submode 2 Design 1 for FIG. 1B.

TABLE 29 and TABLE 30 respectively illustrate methods to encode (W_(1V), W_(2V))+WB CQI and (W_(1H), W_(2H))+WB CQI according to some embodiments of the present disclosure. In particular, in TABLE 29, subsampled indices in the rank-2 case are 0, 2, 4, and 6, which correspond to four vertical beam selection indices and a single co-phasing factor. In TABLE 29, for the case of rank-2 option 1 case, the W_(2H) indices are subsampled in a way that all the horizontal beams and a single co-phasing factor are selected.

TABLE 29 (W_(1V), W_(2V)) + WB CQI Total number bits for Total number (W_(1V), bits for W_(2V)) + RI (W_(1V), W_(2V)) (W_(1V), W_(2V)) CQI 1 W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) 4 bits  8 bits W_(2V): 0-3 (CW index in Table 8) 2 Option 1: 4 bits 11 bits W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) W_(2V): 0-3 (CW index in Table 11) Option 2: W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) W_(2V): 0, 2, 4, 6 (CW in Table 13)

TABLE 30 (W_(1H), W_(2H)) + WB CQI Total number Total number bits for bits for (W_(1H), W_(2H)) + RI (W_(1H), W_(2H)) (W_(1H), W_(2H)) CQI 1 W_(1H): 0, 8 (1^(st) PMI i₁ in Table 3) 4 bits  8 bits W_(2H): 0, 2, 4, 6, 8, 10, 12, 14 (i_(2H) index in Table 8) 2 Option 1: 4 bits 11 bits W_(1H): 0, 8 (1^(st) PMI i₁ in Table 4) W_(2H): 0, 2, 4, 6, 8, 10, 12, 14 (i_(2H) index in Table 11) Option 2: W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) W_(2H): 0-3 (i_(2H) index in Table 13)

FIG. 14 illustrates PUCCH feedback over multiple subframes according to some embodiments of the current invention, wherein WB (W_(2V), W_(2V))+CQI and WB (W_(1V), W_(1H))+CQI are transmitted in PMI/CQI reporting instances. FIG. 14 illustrates PUCCH mode 1-1 Submode 2.

TABLE 31 and TABLE 32 respectively illustrate methods to encode WB (W_(1V), W_(1H))+CQI and WB (W_(2V), W_(2H))+CQI. This design aims to improve the reliability of the second H-PMI and V-PMI. Since as the second H-PMI and V-PMI are used to capture the short term and frequency selective properties of the channels, the feedback frequency may have large impact on the feedback accuracy. In this design shown in FIG. 14, jointly encoded WB (W_(2V), W_(2H)) and WB CQI, are fed back more frequently than the jointly encoded WB (W_(1V), W_(1H)) and WB CQI.

TABLE 31 WB (W_(1V), W_(1H)) + CQI Total number bits for Total number (W_(1V), bits for W_(1H)) + RI (W_(1V), W_(1H)) (W_(1V), W_(1H)) CQI 1 W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) 4 bits  8 bits W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 3) 2 W_(1V): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4) 4 bits 11 bits W_(1H): 0, 4, 8, 12 (1^(st) PMI i₁ in Table 4)

TABLE 32 WB (W_(2V), W_(2H)) + CQI Total number Total bits for number (W_(2V), bits for W_(2H)) + RI Subsampling for (W_(2V), W_(2H)) (W_(2V), W_(2H)) CQI 1 W_(2V): 0, 2 (i_(2V) index in Table 8) 4 bits  8 bits W_(2H): 0, 2, 4, 6, 8, 10, 12, 14 (i_(2H) index in Table 8) 2 Option 1: 4 bits 11 bits W_(2V): 0, 2 (i_(2V) index in Table 11) W_(2H): 0, 2, 4, 6, 8, 10, 12, 14 (i_(2H) index in Table 11) Option 2: W_(2V): 0, 4, (i_(2V) index in Table 13) W_(2H): 0-7 (i_(2H) index in Table 13)

PUCCH Mode 2-1

In PUCCH mode 2-1, RI and PTI are transmitted in the RI reporting instances. The PUCCH reporting when PTI=0 is illustrated in FIG. 15. FIG. 15 illustrates PUCCH mode 2-1 design 1 for FIG. 1B with PTI=0. (W_(1V), W_(1H)) is reported in those subframes for W_(1H) reporting. WB (W_(2V), W_(2H))+CQI are reported in those subframes for WB (W_(2V), W_(2H))+CQI reporting.

The present disclosure addresses an inevitable issue for FD-MIMO standardization (periodic CSI feedback and codebook subsampling): the PUCCH can carry up to only 11 bits, and periodic CSI feedback contents in each subframe should be less than or equal to 11 bits. In addition, it is also desirable to keep the number of bits as small as possible to improve the reception reliability at the BS. For example, the decoding reliability of 3 bit information is better than 5 bit information because the coding rate of the Reed-Muller (RM) code gets decreased. An increased number of bits to feedback CSI for FD-MIMO is likely, and presents a challenge of how to multiplex CSI to fit in (or to reliably transmit) that information on PUCCH. This disclosure addresses that challenge of reliable transmission of periodic CSI feedback.

Comprehensive coverage on PUCCH feedback signaling is a second aspect of the present disclosure. The may be many alternatives for the exact method for PUCCH feedback signaling A comprehensive set of such methods has been illustrated herein by description of the most promising for PUCCH feedback signaling, especially for PUCCH mode 1-1 and 2-1. The alternatives described include options for constructing PUCCH mode 1-1 submode 1 (i.e., RI+W_(1H) reporting in RI reporting instances and W_(2H)W_(2V)+CQI reporting in CQI/PMI reporting instances; RI+W_(1H) reporting in RI reporting instances and W_(2H)+W_(2V)+CQI and W_(2H)+CQI time multiplexed in CQI/PMI reporting instances; and RI+W_(1H) reporting in RI reporting instances and W_(2H)+CQI reporting in CQI/PMI reporting instances). Options for construction of PUCCH mode 1-1 submode 2 and mode 2-1 are also described, together with subsampling methods for these PUCCH modes. This disclosure also exploits advantages of a single CSI process feedback over a multiple CSI process feedback, specifically: a wider range of UEs can support FD-MIMO CSI feedback (UE capacity); and coordinated multipoint (CoMP) extension is straightforward (a multiple CSI process can be implemented only for CoMP).

The overall codebook structure employed in the present disclosure is a Kronecker Product: W=W_(V){circle around (×)}W_(H), where W_(V) is a vertical codebook and W_(H) is a horizontal codebook. The vertical codebook W_(V) is a 2-Tx codebook, a special form of the double codebook structure based upon W_(1V), the identity matrix (which need not be fed back) and W_(2V), a Release-8 2-Tx codebook. The horizontal codebook W_(H) is a Release-10 8-Tx codebook, also a double codebook structure W_(H)=W_(1H)W_(2H), where W_(1H) is a block diagonal matrix and W_(2H) is chosen for beam selection and co-phasing.

For a rank-1 codebook, a rank-1 codeword W is constructed such that both W_(V) and W_(H) are a rank-1 precoding vector, e.g., W_(V) may be a 2×1 precoding vector and W_(H) may be a 8×1 precoding vector so that W is a 16×1 precoding vector. For a rank-2 codebook, in one set a rank-2 codeword W is constructed by rank-1 W_(V) and rank-2 W_(H), e.g., W_(V) may be a 2×1 precoding vector (2-Tx rank-1 codeword) and W_(H) may be a 8×2 precoding matrix (8-Tx rank-2 codeword) such that W is a 16×2 precoding matrix. In an alternative set for a rank-2 codebook, a rank-2 codeword W is constructed by a rank-2 W_(V) and a rank-1 W_(H), e.g., W_(V) may be a 2×2 precoding matrix (2-Tx rank-2 codeword) and W_(H) may be a 8×1 precoding vector (8-Tx rank-1 codeword) such that W is a 16×2 precoding matrix.

For PUCCH mode 1-1 submode 1, a first alternative for submode 1 employs subframe report timing as illustrated in FIG. 2, and RI and W_(1H) joint encoding in accordance with Release 8 encoding for such parameters is sufficient:

TABLE 33 Value of joint encoding of RI and the first PMI I_(RI/PMI1) RI Codebook index i₁ 0-7  1 2I_(RI/PMI1) 8-15 2 2(I_(RI/PMI1) − 8) W_(1H)+RI coding in the RI reporting instances can be kept the same as in Release 8. For W_(2V)+W_(2H)+CQI, subsampling is necessary to keep the same number of feedback bits as in Release 10.

The first alternative for submode 1 employs rank 1 W_(2V) subsampling for V-PMI (illustrated in FIGS. 16A, 16B and 17), with W_(2V) ∈ {0,1} or {0,2}:

${{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ {- 1} \end{bmatrix}}\mspace{14mu} {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ 1 \end{bmatrix}}},{\theta_{0} = {90{^\circ}\text{:}{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ 1 \end{bmatrix}}}},{{a(v)} = {\left\lbrack {1,^{{- j}\; v}} \right\rbrack^{T}\mspace{14mu} {with}}}$ $v:={\frac{2\pi \; d_{V}}{\lambda_{c}}\cos \mspace{11mu} {\theta_{0}.}}$

For example, α(ν)=[1, j]^(T) if

${v = \frac{3\pi}{2}};$

or θ₀=120° with

$\frac{2\pi \; d_{V}}{\lambda_{c}} = {\pi.}$

Although [1, j] is more frequently employed, [1, −1] could be a better choice for MU-MIMO. This disclosure describes both subsampling of {[1, 1], [1, j]} and {[1, 1], [1, −1]}, as well as subsampling that is higher-layer configurable between the two.

The first alternative for submode 1 also employs rank 1 W_(2H) subsampling, with W_(2H) ∈ {0,1, . . . , 7}:

TABLE 34 i₂ i₁ 0 1 2 3 4 5 6 7 0-15 W_(2i) ₁ _(,0) ⁽¹⁾ W_(2i) ₁ _(,1) ⁽¹⁾ W_(2i) ₁ _(,2) ⁽¹⁾ W_(2i) ₁ _(,3) ⁽¹⁾ W_(2i) ₁ _(+1,0) ⁽¹⁾ W_(2i) ₁ _(+1,1) ⁽¹⁾ W_(2i) ₁ _(+1,2) ⁽¹⁾ W_(2i) ₁ _(+1,3) ⁽¹⁾ $W_{m,n}^{(1)} = {\frac{1}{\sqrt{8}}\begin{bmatrix} v_{m} \\ {\phi_{n}v_{m}} \end{bmatrix}}$

TABLE 35 Codebook for 1-layer CSI reporting using antenna ports 15 to 22 i₂ i₁ 0 1 2 3 4 5 6 7 0-15 W_(2i) ₁ _(,0) ⁽¹⁾ W_(2i) ₁ _(,1) ⁽¹⁾ W_(2i) ₁ _(,2) ⁽¹⁾ W_(2i) ₁ _(,3) ⁽¹⁾ W_(2i) ₁ _(+1,0) ⁽¹⁾ W_(2i) ₁ _(+1,1) ⁽¹⁾ W_(2i) ₁ _(+1,2) ⁽¹⁾ W_(2i) ₁ _(+1,3) ⁽¹⁾ i₂ i₁ 8 9 10 11 12 13 14 15 0-15 W_(2i) ₁ _(+2,0) ⁽¹⁾ W_(2i) ₁ _(+2,1) ⁽¹⁾ W_(2i) ₁ _(+2,2) ⁽¹⁾ W_(2i) ₁ _(+2,3) ⁽¹⁾ W_(2i) ₁ _(+3,0) ⁽¹⁾ W_(2i) ₁ _(+3,1) ⁽¹⁾ W_(2i) ₁ _(+3,2) ⁽¹⁾ W_(2i) ₁ _(+3,3) ⁽¹⁾ ${{where}\mspace{14mu} W_{m,n}^{(1)}} = {\frac{1}{\sqrt{8}}\begin{bmatrix} v_{m} \\ {\phi_{n}v_{m}} \end{bmatrix}}$

In the rank-1 case, W_(2H) indices {0,1,2,3,4,5,6,7} utilizes first and second beams with all four co-phasing factors {1, −1, j, −j}, which equates to 32 DFT beams in the horizontal dimension (same as Release 10 codebook).

The first alternative for submode 1 employs, for W_(2V)+W_(2H)+CQI, a rank 2 subsampling codebook that comprises two sets: a first rank 2 subsampling set for which W_(2V) ∈ {0,1}, rank-1:

${{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ 1 \end{bmatrix}}\mspace{20mu} {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ {- 1} \end{bmatrix}}},$

and W_(2H) ∈ {0,1,2,3}, rank-2, first and second beams (same beam cases) with both co-phasing factors {0, j} corresponding to TABLE 4 with:

${W_{m,m^{\prime},n}^{(2)} = {\frac{1}{4}\begin{bmatrix} v_{m} & v_{m^{\prime}} \\ {\phi_{n}v_{m}} & {{- \phi_{n}}v_{m^{\prime}}} \end{bmatrix}}},{\phi_{m} = ^{j\; \pi \; {n/2}}},{{v_{m} = \left\lbrack {1\mspace{14mu} ^{{j2}\; \pi \; {n/32}}\mspace{14mu} ^{{j4\pi}\; {n/32}}\mspace{14mu} ^{j\; 6\pi \; {n/32}}} \right\rbrack^{T}};}$

and a second rank 2 subsampling set for which W_(2V) is a fixed rank-2 codeword

$\frac{1}{2}\begin{bmatrix} 1 & 1 \\ 1 & {- 1} \end{bmatrix}$

and W_(2H) ∈ {0,1, . . . , 7}, rank-1, corresponding to TABLE 35.

A second alternative for PUCCH mode 1-1 submode 1 employs the timing illustrated in FIG. 3, with W_(2V)+W_(2H)+CQI and W_(2H)+CQI time-multiplexed in CQI reporting instances and with W_(2V)+W_(2H)+CQI feedback content constructed according to previous alternative and W_(2H), W_(2H)+CQI satisfying TABLE 11. Because no subsampling is necessary for W_(2H)+CQI, in this alternative W_(2H) feedback is more reliable.

A third alternative for PUCCH mode 1-1 submode 1 employs the timing illustrated in FIG. 4, with W_(2H)+CQI reported in CQI reporting instances (same as Release 10) and RI+W_(2V)+W_(2H) jointly reported in RI reporting instances, such that subsampling is necessary. When RI=1, W_(2V) ∈ {0,1}, W_(1H) ∈ {0,2,4, . . . , 14} (same as Release 10 subsampling) using:

${{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ 1 \end{bmatrix}}\mspace{20mu} {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ {- 1} \end{bmatrix}}},$

When RI=2, the subsampling codebook comprises two sets: a first subsampling set for which W_(2V) ∈ {0,1}, rank-1:

${{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ 1 \end{bmatrix}}\mspace{20mu} {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 \\ {- 1} \end{bmatrix}}},$

and W_(2H) is interpreted as rank-2, W_(2H) ∈ {0,2,4, . . . , 14} (same as Release 10 subsampling); and a second subsampling set for which W_(2V) is a fixed rank-2 codeword:

$\frac{1}{2}\begin{bmatrix} 1 & 1 \\ 1 & {- 1} \end{bmatrix}$

And W_(2H) is interpreted as rank-1, W_(2H) ∈ {0,4,8,12} (which is 2× coarser sampling than Release 10). W_(2H) interpretation is thus dependent upon decoded value of RI and W_(2V). This alternative results in less aggressive subsampling for W_(2H), but also results in a need for W_(2V) to additionally be carried on RI reporting instances.

For PUCCH mode 1-1 submode 2, in one embodiment RI is separately fed back in RI reporting instances, which requires that W_(1H), W_(2H), and W_(2V) be sent in CQI reporting instances. One option is time multiplexing of (W_(1H), W_(2V), CQI) and (W_(1H), W_(2H), CQI) (see FIG. 5); another option is time multiplexing of (W_(1H), W_(2V), CQI) and (W_(2H), CQI) (see FIG. 6). Subsampling is necessary for some of these PMI/CQI feedback methods, and the subsampling methods described above for alterative 1 can be employed. By way of comparison, in Release 10 PUCCH mode 1-1 submode 2 RI is separately fed back and WB (W₁, W₂)+WB CQI are reported in CQI reporting instances.

For PUCCH mode 2-1, in one embodiment when the most recently reported PTI=0, W_(1H) and (W_(2V), W_(2H), CQI) are time multiplexed in CQI/PMI reporting instances (see FIG. 7). When the most recently reported PTI=1, WB (W_(2V), W_(2H), CQI) and SB (W_(2V), W_(2H), CQI) are time multiplexed in CQI/PMI reporting instances (see FIGS. 8A and 8B).

The present disclosure also addresses an important issue for FD-MIMO standardization: feedback overhead and complexity reduction for double-codebook based FD-MIMO feedback coding. A major issue with FD-MIMO CSI feedback would be the complexity and overhead for CQI feedback, as the codebook size is almost certain to increase for FD-MIMO. This disclosure suggests a promising method to reduce the codebook size for FD-MIMO codebook without losing any performance, and also suggests two different ways of constructing rank-2 codebook, with partitioning information on co-phasing and two beams into H and V second PMI.

Cross-polarized (x-pol) is the most important antenna configuration to be considered in FD-MIMO and x-pol has been almost exclusive studied during the standardization. The benefits of x-pol against widely spaced antennas are in terms of BS antenna panel form factor and performance; with x-pol it has been observed in SLS that rank-2 is quite easily achieved which could improve throughput by 2×; on the other hand widely spaced co-pot may suffer from interference due to grating lobes.

Straightforward design of Kronecker product codebook incurs huge UE complexity, so standardization should provide complexity reduction of the type disclosed in this disclosure. Codebook subset restriction could be sufficient for the FD-MIMO codebook design. Optimal designs may depend upon whether FD-MIMO will support up to 8 or 16 antenna ports, or up to 64 ports.

For cross-polarized (x-pol) antenna arrays or sub-arrays, co-phasing in both H and V codebooks is unnecessary. By getting rid of co-phasing from either H or V, 2 bits can be saved without losing performance, a 4X complexity savings resulting in 16384 codewords. The rank-2 codebook construction may employ one beam for V, two beams and co-phasing for H, or one beam and co-phasing for V, two beams for H. PUCCH codebook subsampling reduces complexity and overhead.

The FD-MIMO double codebook structure proposed in this disclosure include vertical and horizontal codebooks defined as:

${W_{1V} = \left\{ {\begin{matrix} {X_{V}\left( i_{V} \right)} & 0 \\ 0 & {X_{V}\left( i_{1V} \right)} \end{matrix},{i_{1V} = 0},1,\ldots \;,15} \right\}},{W_{1H} = \left\{ {\begin{matrix} {X_{H}\left( i_{H} \right)} & 0 \\ 0 & {X_{H}\left( i_{1H} \right)} \end{matrix},{i_{1H} = 0},1,\ldots \;,15} \right\}},$

where W_(1V) and W_(1H) are selected to be a 4×4 matrix X(i) defined as in the following:

X(i)

[ν_(2imod32) ν_((2i+1)mod32) ν_((2i+2)mod32) ν_((2i+3)mod32)]

with ν_(n)=[1 e^(j2πn/32) e^(j2π2n/32) e^(j2π3n/32)]^(T) and with i=0,1, . . . , 15. In the first codebooks W₁ (size 32×32), i_(1V) and i_(1H) determines a set of beams:

$\mspace{20mu} {{W_{1} = \begin{Bmatrix} {{X_{V}\left( i_{1V} \right)} \cdot {X_{H}\left( i_{1H} \right)}} & 0 \\ 0 & {{X_{V}\left( i_{1V} \right)} \cdot {X_{H}\left( i_{1H} \right)}} \end{Bmatrix}},{{i_{1V} \cdot i_{1H}} = {\left\lbrack {{v_{2i_{1V}{mod}\; 23} \otimes v_{2i_{1H}{mod}\; 32}}\mspace{11mu} {v_{2i_{1V}{mod}\; 32} \otimes v_{{({{2i_{1H}} + 1})}{mod}\; 32}}\mspace{11mu} \ldots \mspace{11mu} {v_{{({{2i_{1V}} + 3})}{mod}\; 32} \otimes v_{{({{2i_{1H}} + 3})}{mod}\; 32}}} \right\rbrack.}}}$

In the first codebooks W₂, i_(2V) and i_(2H) give beam selection and co-phasing.

In constructing the FD-MIMO double codebook, for each polarization, a Kronecker product is applied or H and V beams (ν_(m) and 84 _(m′)) to construct a 16×1 vector. Co-phasing on the two Kronecker product beams of the two polarizations is applied to construct a rank-1 precoder. The one to one mapping between antenna port and cross-polarized antenna elements is illustrated in FIG. 18. Note that if (4+4) and (4+4) bits are used for H and V domain, total number of bits for the codebook is 16 bits, which is too many to fit in a single PUCCH format 2, and likely can be further optimized in terms of feedback overhead.

For one design of an overhead efficient rank-1 codebook construction, a beamforming vector corresponding to index pair (m, m′) and co-phasing n is formed as

${w_{m,m^{\prime},n} = {\frac{1}{\sqrt{32}}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} \end{bmatrix}}},$

where φ_(n)=e^(jnπ/2), n=0,1,2,3 and where m is a function of i_(1V) and i_(2V) and (m′, n) is a function of i_(1H) and i_(2H):

TABLE 36 W_(2H) 0 1 2 3 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,3) 4 5 6 7 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,3) 8 9 10 11 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,3) 12 13 14 15 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,2) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,3) $w_{m,m^{\prime},n} = {\frac{1}{\sqrt{32}}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} \end{bmatrix}}$ In TABLE 36, m=2i_(1V)+i_(2V), i_(2V) ∈ {0,1,2,3}, m′=2i_(1H)+└i_(2H)/4┘, n=i_(2H) mod 4, and i_(2H) ∈ {0,1, . . . , 15}. Co-phasing need not be applied to both H and V domains. By eliminating co-phasing from the V domain, resulting in (4+2) bits for the V domain while (4+4) bits are employed for the H domain, a 2 bit savings is achieved without losing performance.

For one option for a rank-2 codebook, a beamforming vector corresponding to index (m, m′, m″) and co-phasing n is formed as

${W_{m,m^{\prime},m^{''},n}^{(2)} = {\frac{1}{8}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{''}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{''}}}} \end{bmatrix}}},$

where m is a function of i_(1V) and i_(2V) (same as the rank-1 design just described) and (m′, m″, n) is a function of i_(1H) and i_(2H) (that is, the horizontal codebook may be the same at Release 10 8 Tx):

TABLE 37 W_(2H) 0 1 2 3 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+1,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+1,1) 4 5 6 7 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,2i) _(1H) _(+2,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+2,2i) _(1H) _(+2,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,2i) _(1H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+3,2i) _(1H) _(+3,1) 8 9 10 11 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(+1,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(+1,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+2,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(+1,2i) _(1H) _(+2,1) 12 13 14 15 w_(2i) _(1V) _(+i) _(2V) _(,2i) _(1H) _(,2i) _(1H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(2H) _(,2i) _(2H) _(+3,1) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(2H) _(+1,2i) _(2H) _(+3,0) w_(2i) _(1V) _(+i) _(2V) _(,2i) _(2H) _(+1,2i) _(2H) _(+3,1) $w_{m,m^{\prime},m^{''},n} = {\frac{1}{8}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{''}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{''}}}} \end{bmatrix}}$ In TABLE 37, m=2i_(1V)+i_(2V), i_(2V) ∈ {0,1,2,3}, m′=2i_(1H)+f₁(i_(2H)), m″=2i_(1H)+f₂(i_(2H)), (i_(2H)), n=i_(2H) mod 2, and i_(2H) ∈ {0,1, . . . , 15}.

For a second option for a rank-2 codebook, a beamforming vector corresponding to index (m, m′, m″) and co-phasing n is formed as

${W_{m,m^{\prime},m^{''},n}^{(2)} = {\frac{1}{8}\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{''}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{''}}}} \end{bmatrix}}},{\phi_{n} = ^{j\; n\; \pi}},{n = 0},1,$

where (m, n) is a function of i_(1V) and i_(2V), (m′, m″) is a function of i_(1H) and i_(2H):

TABLE 38 W_(2V) indices (m, n) W_(2V) indices (m′, m″) 0 (0, 0) 0 (0, 0) 1 (0, 1) 1 (1, 1) 2 (1, 0) 2 (2, 2) 3 (1, 1) 3 (3, 3) 4 (2, 0) 4 (0, 1) 5 (2, 1) 5 (1, 2) 6 (3, 0) 6 (0, 3) 7 (3, 1) 7 (3, 0) In TABLE 38, m=2i_(1V)+└i_(2V)/2┘, i_(2V) ∈ {0, . . . , 7}, n=i_(2V) mod 2, m′=2i_(1H)+f₁(i_(2H)), m″=2i_(1H)+f₂(i_(2H)), and i_(2H) ∈ {0, . . . , 7}. In this design, information is balanced between H and V feedback, which is beneficial for PUCCH.

In PUCCH feedback for one alternative for PUCCH Mode 1-1, submode 1, RI, W_(1H) and W_(1V) are jointly encoded and fed back in RI reporting instances (see FIG. 11), while W_(2V), W_(2H) and CQI are fed back in CQI/PMI reporting instances. In the RI+W_(1H)+W_(1V) joint encoding, beams are uniformly subsampled (see TABLE 24). The W_(2V)+W_(2H)+CQI reporting, for rank 1, employs uniform beam subsampling (1 bit) for W_(2V) and uniform co-phase subsampling (3 bits) for W_(2H) (see TABLE 17, values m=0 for i_(2V)=0 and m=2 for i_(2V)=2 and values {0,0} for {m′, n} when i_(2H)=0, {0,2} when i_(2H)=2, {1,0} when i_(2H)=4, {1,2} when i_(2H)=6, {2,0} when i_(2H)=8, {2,2} when i_(2H)=10, {3,0} when i_(2H)=12, and {3,2} when i_(2H)=14). One option for the W_(2V)+W_(2H)+CQI reporting, for rank 2, employs uniform beam subsampling (1 bit) for W_(2V) and all combinations of same-beam pairs (3 bits) for W_(2H) (see TABLE 20, values m=0 for i_(2V)=0 and m=2 for i_(2V)=2 and the first two rows for i_(2H) indices). An alternate option for the W_(2V)+W_(2H)+CQI reporting, for rank 2, employs uniform beam subsampling (2 bits) for W_(2V) and all combinations of same-beam pairs (2 bits) for W_(2H) (see TABLE 22, values (m, n)=(0,0) for i_(2V)=0, (m, n)=(0,1) for i_(2V)=1, (m,)=(1,0) for i_(2V)=2, (m, n)=(2,0) for 1_(2V)=4, and (m, n)=(2,1) for i_(2V)=5, and the first three rows for i_(2H) indices).

In PUCCH feedback for another alternative for PUCCH Mode 1-1, submode 1, (RI, W_(1H) and W_(1V)) are jointly encoded and fed back in RI reporting instances (see FIG. 12), while (W_(2V), CQI) and (W_(2H), CQI) are time multiplexed in CQI/PMI reporting instances. For one option, TABLE 20 is employed. For a second option, no subsampling is necessary for W_(2V), W_(2H) reporting (see TABLE 22).

In PUCCH feedback for PUCCH Mode 1-1, submode 2, only RI is reported in RI reporting instances (see FIG. 12), while (W_(1V) W_(2V), CQI) and (W_(1H), W_(2H), CQI) are time multiplexed in CQI/PMI reporting instances. For (W_(1V), W_(2V), CQI) reporting, if RI=1, uniformly subsampled beam indices {0,4,8,12} are employed for W_(1V) and no subsampling is necessary (i_(2V){0,1,2,3}) for W_(2V). If RI=2, uniformly subsampled beam indices {0,4,8,12} are employed for W_(1V) and either no subsampling is necessary (i_(2V){0,1,2,3}) or all combinations of same-beam pairs (i_(2V)={0,1,4,5}, (m, n)=(0,0), (0,1), (2,0), (2,1)) are employed for W_(2V). For (W_(1V), W_(2V), CQI) reporting, if RI=1, uniformly subsampled beam indices {0,8} are employed for W_(1H) and indices i_(2V)={0,2,4, . . . , 14} are employed for W_(2H) (see corresponding i_(2H) entries in TABLE 17). If RI=2, uniformly subsampled beam indices {0,8} are employed for W_(1H) and either indices i_(2H)={0, . . . , 7} or all combinations of same-beam pairs (i_(2H)={0,1,2,3}) are employed for W_(2H) (see corresponding i_(2H) values in TABLE 20 and TABLE 22, respectively).

Although the present disclosure has been described with an exemplary embodiment, various changes and modifications may be suggested to one skilled in the art. It is intended that the present disclosure encompass such changes and modifications as fall within the scope of the appended claims. 

What is claimed is:
 1. A user equipment, comprising: a transceiver configured to communicate with at least one base station; and processing circuitry configured to control the transceiver to: receive a set of channel state information reference signals (CSI-RS); estimate channels based on the received CSI-RS; derive a channel quality indicator (CQI) based on the channel estimates and a precoding matrix; and report the CQI and at least a first and a second precoding matrix indicator (PMI) i_(2V) and i_(2H), wherein at least a first index m, a second index m′, and a third index n are determined based upon the first and the second PMI i_(2V) and i_(2H) and a third and a fourth PMI i_(1V) and i_(1H), wherein the indices m, m′ and n are employed to select the precoding matrix, wherein the selected precoding matrix includes a first column comprising a first row partition and a second row partition, wherein the first row partition is a Kronecker product of at least first and second precoding vectors ν_(m) and ν_(m′) and the second row partition is a Kronecker product of a first term and a second term, wherein the first term is a product of a co-phasing factor φ_(n) and the first precoding vector ν_(m) and the second term is the second precoding vector ν_(m′), and wherein the first precoding vector ν_(m) is selected from a first codebook and the second precoding vector ν_(m′) is selected from a second codebook.
 2. The user equipment according to claim 1, wherein the report of the CQI and the PMI is made on a PUCCH and wherein a report prior to the report on the PUCCH includes the third and the fourth PMI i_(1V) and i_(1H).
 3. The user equipment according to claim 2, wherein subsampling of the second PMI i_(2H) selects even-numbered entries.
 4. The user equipment according to claim 2, wherein subsampling of the second PMI i_(2H) selects the first half of entries within a set of entries for the second PMI i_(2H).
 5. The user equipment according to claim 1, wherein the report of the CQI and the PMI is made on a PUSCH, wherein the report of the CQI and the PMI on the PUSCH is for subband and a report of the third and the fourth PMI i_(1V) and i_(1H) on the PUSCH is for wideband.
 6. The user equipment according to claim 1, wherein the precoding matrix indicators relate to a rank-1 precoding matrix w_(m,m′,n) constructed by ${w_{m,m^{\prime},n} = {q\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} \end{bmatrix}}},$ where q is a normalizing factor.
 7. The user equipment according to claim 1, wherein the first codebook, from which the precoding vector ν_(m) is selected, is a Discrete Fourier Transform (DFT) codebook having size N₁ that is oversampled with an oversampling factor o₁ and wherein the second codebook, from which the precoding vector ν_(m′) is selected, is a DFT codebook having size N₂ that is oversampled with an oversampling factor o₂.
 8. The user equipment according to claim 1, wherein the precoding matrix indicators relate to a rank-2 precoding matrix W_(m,m′,m″,n) ⁽²⁾ constructed by ${W_{m,m^{\prime},m^{''},n}^{(2)} = {q\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{''}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{''}}}} \end{bmatrix}}},$ where m″ is a fourth index employed with the indices m, m′ and n to select the rank-2 precoding matrix, ν_(m″) is a third precoding vector selected from the second codebook, and q is a normalizing factor.
 9. The user equipment according to claim 1, wherein the first index m is a function of the first PMI i_(2V) the third PMI i_(1V), the second index m′ is a function of the second PMI i_(2H) and the fourth PMI i_(1H), and the third index n is a function of the second PMI i_(2H).
 10. A base station, comprising: a transceiver configured to communicate with at least one user equipment; and processing circuitry configured to control the transceiver to: transmit a set of channel state information reference signals (CSI-RS); and receive a report of a channel quality indicator (CQI) and at least a first and a second precoding matrix indicator (PMI) i_(2V) and i_(2H), the CQI derived based on channel estimates and a precoding matrix and the channel estimates estimated based on the CSI-RS, wherein at least a first index m, a second index m′, and a third index n are determined based upon the first and the second PMI i_(2V) and i_(2H) and a third and a fourth PMI i_(1V) and i_(1H), wherein the indices m, m′ and n are employed to select the precoding matrix, wherein the selected precoding matrix includes a first column comprising a first row partition and a second row partition, wherein the first row partition is a Kronecker product of at least first and second precoding vectors ν_(m) and ν_(m′) and the second row partition is a Kronecker product of a first term and a second term, wherein the first term is a product of a co-phasing factor φ_(n) and the first precoding vector ν_(m) and the second term is the second precoding vector ν_(m′), and wherein the first precoding vector ν_(m) is selected from a first codebook and the second precoding vector ν_(m′) is selected from a second codebook.
 11. The base station according to claim 10, wherein the report of the CQI and the PMI is made on a PUCCH and wherein a report prior to the report on the PUCCH includes the third and the fourth PMI i_(1V) and i_(1H).
 12. The base station according to claim 11, wherein subsampling of the second PMI i_(2H) selects even-numbered entries.
 13. The base station according to claim 10, wherein subsampling of the second PMI i_(2H) selects the first half of entries within a set of entries for the second PMI i_(2H).
 14. The base station according to claim 10, wherein the report of the CQI and the PMI is made on a PUSCH, wherein the report of the CQI and the PMI on the PUSCH is for subband and a report of the third and the fourth PMI i_(1V) and i_(1H) on the PUSCH is for wideband.
 15. The base station according to claim 10, wherein the precoding matrix indicators relate to a rank-1 precoding matrix w_(m,m′,n) constructed by ${w_{m,m^{\prime},n} = {q\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} \end{bmatrix}}},$ where q is a normalizing factor.
 16. The base station according to claim 10, wherein the first codebook, from which the precoding vector ν_(m) is selected, is a Discrete Fourier Transform (DFT) codebook having size N₁ that is oversampled with an oversampling factor o₁ and wherein the second codebook, from which the precoding vector ν_(m′) is selected, is a DFT codebook having size N₂ that is oversampled with an oversampling factor o₂.
 17. The base station according to claim 10, wherein the precoding matrix indicators relate to a rank-2 precoding matrix W_(m,m′,m″,n) ⁽²⁾ constructed by ${W_{m,m^{\prime},m^{''},n}^{(2)} = {q\begin{bmatrix} {v_{m} \otimes v_{m^{\prime}}} & {v_{m} \otimes v_{m^{''}}} \\ {\phi_{n}{v_{m} \otimes v_{m^{\prime}}}} & {{- \phi_{n}}{v_{m} \otimes v_{m^{''}}}} \end{bmatrix}}},$ where m″ is a fourth index employed with the indices m, m′ and n to select the rank-2 precoding matrix, ν_(m″) is a third precoding vector selected from the second codebook, and q is a normalizing factor.
 18. The base station according to claim 10, wherein the first index m is a function of the first PMI i_(2V) the third PMI i_(1V), the second index m′ is a function of the second PMI i_(2H) and the fourth PMI i_(1H), and the third index n is a function of the second PMI i_(2H).
 19. A method, comprising: transmitting, from a base station, a set of channel state information reference signals (CSI-RS); and receiving, at the base station, a report from a user equipment of a channel quality indicator (CQI) and at least a first and a second precoding matrix indicator (PMI) i_(2V) and i_(2H), the CQI derived based on channel estimates and a precoding matrix and the channel estimates estimated based on the CSI-RS, wherein at least a first index m, a second index m′, and a third index n are determined based upon the first and the second PMI i_(2V) and i_(2H) and a third and a fourth PMI i_(1V) and i_(1H), wherein the indices m, m′ and n are employed to select the precoding matrix, wherein the selected precoding matrix includes a first column comprising a first row partition and a second row partition, wherein the first row partition is a Kronecker product of at least first and second precoding vectors ν_(m) and ν_(m′) and the second row partition is a Kronecker product of a first term and a second term, wherein the first term is a product of a co-phasing factor φ_(n) and the first precoding vector ν_(m) and the second term is the second precoding vector ν_(m′), and wherein the first precoding vector ν_(m) is selected from a first codebook and the second precoding vector ν_(m′) is selected from a second codebook.
 20. The method according to claim 19, wherein the report of the CQI and the PMI is made on a PUCCH and wherein a report prior to the report on the PUCCH includes the third and the fourth PMI i_(1V) and i_(1H). 